CA1216060A - Method and apparatus for optimizing feedhorn performance - Google Patents
Method and apparatus for optimizing feedhorn performanceInfo
- Publication number
- CA1216060A CA1216060A CA000447751A CA447751A CA1216060A CA 1216060 A CA1216060 A CA 1216060A CA 000447751 A CA000447751 A CA 000447751A CA 447751 A CA447751 A CA 447751A CA 1216060 A CA1216060 A CA 1216060A
- Authority
- CA
- Canada
- Prior art keywords
- feedhorn
- aperture
- circular waveguide
- aperture end
- plane
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
Classifications
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
- H01Q19/10—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces
- H01Q19/12—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces wherein the surfaces are concave
- H01Q19/13—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using reflecting surfaces wherein the surfaces are concave the primary radiating source being a single radiating element, e.g. a dipole, a slot, a waveguide termination
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/06—Waveguide mouths
- H01Q13/065—Waveguide mouths provided with a flange or a choke
Abstract
ABSTRACT
An optimized feedhorn comprising a circular waveguide having a corrugated plate disposed around the outside of the aperture of the waveguide wherein the corrugations of the plate are capacitive as to E plane signals. The feedhorn includes a reduced aperture diameter which selectively protrudes beyond the plane of the corrugated plate. The amount of protrusion of the aperture is determined to approximately equalize E and H plane beamwidths and selectively shape the top and skirts of the signal pattern around the center frequency of interest.
An optimized feedhorn comprising a circular waveguide having a corrugated plate disposed around the outside of the aperture of the waveguide wherein the corrugations of the plate are capacitive as to E plane signals. The feedhorn includes a reduced aperture diameter which selectively protrudes beyond the plane of the corrugated plate. The amount of protrusion of the aperture is determined to approximately equalize E and H plane beamwidths and selectively shape the top and skirts of the signal pattern around the center frequency of interest.
Description
1 ~Z~
METHOD AND APP~RATUS FOR
-OPTIMIZING FEEDHORN PERFORMANCE
Background and Summary of the Invention In the design of antennas Eor communications satellite systems, there are several important design consid-erations. The desired antenna should provide maximum signal gain, introduce minimum noise into the system and exhibit relatively low side-lobe signal levels. Such receiving antennas typically utilize a prime focus feedhorn to illumin-ate a parabolic reflector so as to achieve the best compromiseamong the listed design considerations.
To provide maximum signal gain, uniform illumination across the entire parabolic reflector is desirable but conflicts with the requirement for minimum noise and low side-lobe levels which demand a highly tapered illumination.
Tapered illumination refers to illumination of the center of the reflector and utilizing the outer edge of the reflector as a shield from thermal noise radiated from earth.
Theoretically, the minimum noise and maximum gain requirements of antenna design can be met by uniformly illuminating the parabolic reflector with a feedhorn which emits a signal having infinitely steep side boundaries of its signal pattern (hereafter "skirts"). Practically, such illumination can only be approached by selecting a parabolic reflector having a focal length to diameter
METHOD AND APP~RATUS FOR
-OPTIMIZING FEEDHORN PERFORMANCE
Background and Summary of the Invention In the design of antennas Eor communications satellite systems, there are several important design consid-erations. The desired antenna should provide maximum signal gain, introduce minimum noise into the system and exhibit relatively low side-lobe signal levels. Such receiving antennas typically utilize a prime focus feedhorn to illumin-ate a parabolic reflector so as to achieve the best compromiseamong the listed design considerations.
To provide maximum signal gain, uniform illumination across the entire parabolic reflector is desirable but conflicts with the requirement for minimum noise and low side-lobe levels which demand a highly tapered illumination.
Tapered illumination refers to illumination of the center of the reflector and utilizing the outer edge of the reflector as a shield from thermal noise radiated from earth.
Theoretically, the minimum noise and maximum gain requirements of antenna design can be met by uniformly illuminating the parabolic reflector with a feedhorn which emits a signal having infinitely steep side boundaries of its signal pattern (hereafter "skirts"). Practically, such illumination can only be approached by selecting a parabolic reflector having a focal length to diameter
2 ~ 3 ratio (f/D) matched to the performance of an op-timized feedhorn.
To optimize carrier (signal)-to-noise ratio (C/N), consideration must be given -to the amplifier to which the feedhorn is coupled. While ten years ago, very high temperature amplifiers (on the order of 600 Kelvin (K)) were used, commonly 100K are now the industry standard with 75K units becoming available.
One well-known prior art feedhorn available on the market tod y maximizes C/N on a 0.375 f/D antenna using a 120K amplifier. The feedhorn comprises a circular waveguide having a corrugated plate disposed around the outside of the aperture at one end of the waveguide and including a 1/4 wave transformer at the other end of the waveguide for impedance matching and coupling to the amplifier. See, for example, U.S. Patents 272,910 (Design) and 4,415,516 issued March 6, 1984 and November 8, 1983 respectively, and assigned to the assignee hereof.
Such a feedhorn provides relatively uniform illumination across the parabolic reflector, its characteristic signal over the bandwidth of interest having relatively steep skirts and a substantially flat top by properly selecting the diameter of the circular waveguide for the center frequency of interest, and by properly locating the corrugated plate with respect to the outside of the a~erture of the waveguide.
With advances in amplifier technology, the need for further advancement of antenna technology is clear. ~road bandwidth and wide
To optimize carrier (signal)-to-noise ratio (C/N), consideration must be given -to the amplifier to which the feedhorn is coupled. While ten years ago, very high temperature amplifiers (on the order of 600 Kelvin (K)) were used, commonly 100K are now the industry standard with 75K units becoming available.
One well-known prior art feedhorn available on the market tod y maximizes C/N on a 0.375 f/D antenna using a 120K amplifier. The feedhorn comprises a circular waveguide having a corrugated plate disposed around the outside of the aperture at one end of the waveguide and including a 1/4 wave transformer at the other end of the waveguide for impedance matching and coupling to the amplifier. See, for example, U.S. Patents 272,910 (Design) and 4,415,516 issued March 6, 1984 and November 8, 1983 respectively, and assigned to the assignee hereof.
Such a feedhorn provides relatively uniform illumination across the parabolic reflector, its characteristic signal over the bandwidth of interest having relatively steep skirts and a substantially flat top by properly selecting the diameter of the circular waveguide for the center frequency of interest, and by properly locating the corrugated plate with respect to the outside of the a~erture of the waveguide.
With advances in amplifier technology, the need for further advancement of antenna technology is clear. ~road bandwidth and wide
3 1~160~
beamwidth for uniform illumination of the parabolic reflector and steep side skirts of the emitted signal pattern is requiredto meet improved amplifier performance. The ideal signal pattern is flat-topped, having infinitely steep skirts. Furthermore, the pattern should be approximately equal (symmetrical) in the E and H planes which are orthogonal to each other.
E and H plane symmetry is desirable because most communi-cations satellites in use today emit two ort.hogonal signals which must be received. To achieve E and H plane symmetry the aperture of the feedhorn in the E plane should be smaller than that in the H
plane. This corfiguration arises because the electric ~ield of the H
plane is sinusoidally distributed across the diameter of the waveguide and there i~ no curren~-in the sidewalls of the waveguide.
However, the electric field of the E plane causes current to flow in the sidewalls of the waveguide which, upon reaching the aperture, flows down the outside of the waveguide and makes the aperture appear larger. Thus, by reducing the E plane dimension appropriately, the critically equivalent apertur~s for approximately equal E and H plane beamwidths are produced.
A circular waveguid~ is used in most present-day feedhorns because it is the most convenient way to receive the two orthogonal signals transmitted by communications satellites, However, obviously it is not possible to reduce only E plane beamwidths by reducing the aperture of a circular waveguide in one dimension without simulta-neously affecting the other dimension which affects H plane beam-width.
It is well understoc~ that signal beamwidth can be con-trolled by changing aperture size. The smaller the aperture, the wider the pattern for both the E and ~ plane beamwidths. It is also well understood that beamwidth can be controlled by adding a plzte around the aperture of the circular waveguide of the feedhorn, such plates having various configurations, sizes and location behind the aperture. Depending on location, the aperture of the circular wave-guide appears to protrude beyond the plane of the plate~
Location of the plate with respect to the aperture primarily affects the E plane beamwidth since it is interacts with the current flowing down the outside of the waveguide. When the current reaches the plate, it is reflected back toward the aperture.
If that current is at the proper amplitude and in the proper phase when re-introduced at the aperture, it augments the signal pattern emitted by the feedhorn. An equivalent explanation found in the literature refers to excitation of higher order modes which reinforce the principal TE11 mode in the waveguide.
If tho diameter of the aperture of the circular waveguide is reduced by decreasing the diameter of the wavesuide along its entire length, severe impedance mismatch is produced. To overcome that impedance mismatch at the center frequency of interest, the circular waveguide must be lengthened substantially. The longer the waveguide, the more unwieldy th~ feedhorn is to mount, rotate or otherwise conveniently use. According to the present invention, however, E plane signal beamwidth can be controlled by reducing the diameter of the circular waveguide just at the aperture by insertion 5 ~ u of a small annular iris. Impedence match of the feedhorn is thus only slightly compromised.
In practice, location of the plate around the aperture affects both the E and H plane signal patterns. The effect is greater for the E plane than for the H plane, which is expected because of the E
plane current flowing in the walls of the waveguide.
A feedhorn constructed in accordance with the principles of the present invention comprises a circular waveguide having a corrugated plate disposed around the outside of the aperture of the waveguide wherein the corrugations of the plate are capacitive as to E plane signals. In addition, the feedhorn of the present invention includes a reduced aperture diameter which selectively protrudes beyond the plane of the corrugated plate. The amount of protrusion of the aperture is determined to approximately equalize E and H plane beamwidths and selectively shape the top and skirts of signal pattern around the center frequency of interest. Aperture diameter is reduced primarily to control beamwidth for uniform illumination across the entire area of the parabolic reflector.
Various aspects of the invention are as follows:
Apparatus for optimizing performance of a feedhorn with a parabolic reflector in an antenna system, said feedhorn including a circular waveguide for receiving polarized sig~als at an aperture end, impedance matching means coupled to the other end and a corrugated plate disposed around the outside of the circular waveguide near the aperture end, said apparatus comprising an annular iris having an outside diameter approximately equal to the inside diameter of the circular waveguide for interference fit therewith, having an inside diameter determined by the desired beamwidth of the signal to be emitted therefrom, and having a longitudinal dimension selected to protrude beyond the corrugated plate of the feedhorn to approximately equalize the E and H plane beamwidths and selectively shape the signal patterns thereof.
~L6~
5a Method for optimizing performance of a feedhorn ~ith a parabolic reflector in an antenna system, said feedhorn including a circular waveguide for receiving polarized signals at an aperture end, impedance matchin~ means coupled to the other end and a corrugated plate disposed around the outside of the c.ircular waveguide near the aperture end, said method comprising the steps of:
reducing the inside diameter of the aperture end of said circular waveguide of the feedhorn;
protrudirg the aperture end of said circular waveguide of the feedhorn beyond the corrugated plate in an amount equal to that required to approximately equalize the E and H plane beamwidths and selectively shape the signal patterns thereof.
A prime focus feedhorn comprising:
a circular waveguide, having a rear end, an aperture end, and an inside diameter, for receiving polarized signals at the aperture end;
impedance matching means coupled to the rear end for transmitting received signals; and a plate disposed around the outside of 'he circular waveguide near the aperture end havlng corrugations formed by rings thereon concentric with the aperture end;
said aperture end having a diameter selectively less than the inside diameter of the circular waveguide and selectively protruding beyond the plate.
Description of the Drawing Figure lA is a top view of the annular iris constructed according to the principles of the present in~ention.
Figure lB is a sectional view at A-A of the annular iris of Figure lA.
Figure 2 is an exploded sideview of ~ feedhorn incorporating a corrugated plate and the annular iris of Figures lA
6 ~ $V
and ~ according to the present invention.
b~
Figure 3A-D is a graph of the effect on E and H field b ~ -width as a function of aperture protrusion beyond the corrugated plate of prime focus feedhorns including the feedhorn of the present invention incorporating the annular iris of Figures 1A and 1~.
Description of the Preferred Embodiment Referring to Figures 1A and 1B, annular iris 10 according to the preferred embodiment of the present invention is shown having outside diameter 16 inside diameter 12 at its aperture end and longitudinal dimension 14. Inside diameter 13, which is larger than aperture diameter 12 and smaller than outside diameter 16~ can be equal to aperture diameter 1Z for small values of longitudinal dimension 14.
Referring now to Figure 2, outside diameter 16 of annular iris 10 is slightly less than the inside diameter of the circular waveguide )ortion of prime focua feedhorn 20 to provide interference fit as -ri~ 10 is inserted therein. While the interference fit may be sufficient to affix iris 10 to circular waveguide 21, it may be necessary to secure it by using conductive glue, solder, braze or other means for assuring attachment.
Annular iris 10 and feedhorn 20 are both made of aluminum or other suitable materidl which can withstand environmental conditions likely to be encountered and provide the electrical compatibility with the system. While not required, annular iris 10 and feedhorn 20 should be constructed of the same material to avoid 7 ~Z~5~
electrical and electrochemical incompatibilities which may arise from using two different materials. It should be noted that termination of feedhorn 20 at the other end of circular waveguide 21 is not shown, since it is not within the scope of this invention.
Corrugated plate 22 includes corrugaticns formed by rings concentric with aperture 24, shown typically at 25. Preferably, the corrugations are greater than 1/4 wavelength in depth and there are at least 3 of them. By constructing the corrugations deeper than 1~4 wavelength, typically 5/8 wavelength or more, a capacitive reactance is presented to E-plane current flowing on the outside of the feedhorn walls. In addition, the frequency response of feedhorn 20 is approximately flat, less than +1dB, over a broad range of frequencies, e.g. +0.5gHz, around the center frequency of interest.
Thus, the performance of the feedhorn of the present invention is essentially frequency independent around its center frequency.
Dimension 30 refers to the amount in inches of aperture prctrusion beyond corrugated plate 22. Feedhorn 20 may include some fixed aperture protrusion such as that shown at 24. Additional pro-trusion, making up the total protrusion for the feedhorn, is provided by iris 10 and amounts to slightly less than dimension 14, since some of that dimension is consumed when iris 10 is inserted into feedhorn 20 at its aperture 240 Dimension 12 of annular iris 10 affects both E and H plane beamwidth. As stated in this specification, the effect is greater for the E plane pattern. Thus, as dimension 12 is reduced for a given center frequency, E plane beamwidth approaches H plane beamwid'h. 1 2 1 ~ ~tn ~
As protrusion 30 of feedhorn 20 becomes greater, the shape of the E plane signal pattern changes, having steeper skirts and a flatter top, as shown by the three E plane patterns inset above curves 31 and 33 in Figure 3D. The progressive flattening and rippling of the top of a gradually widening E plane pattern in Figures 3A through 3C as aperture protrusion increases is caused by the change in interaction of the re-introduced E plane current with the primary signal at the aperture of the feedhorn. The behavior of H plane pattern is similar, but never becomes as flat on top a~ the wider beamwidths. The Y-axes of Figures 3A-C are in units of dB and the X-axes are in units of angular degrees.
Referring again to Figure 3D, the intersection of curves 31 and 33 indicates approxlmately equalized E and H plane patterns are obtained for a beamwidth of 130 (0.36 f/D reflector) with an aper-ture protrusion of about 0.6". The effect of the present i,vention, selectively reducing the aperture diameter and protruding it beyond a plate having capacitive corrugations, is to shift the intersection of curves 31 and 33 so that approximately equalized E and H plane pat-terns are obtained for a beamwidth of 160 (0.3 ftD reflector) with an aperture protrusion of about 0.9". The improvement of system per-formance in a system utilizing a feedhorn according to the present inventiot. with an 0.3 f/D reflector is reduced electrical noise~
including such noise radiated from thermal sources, introduced into the system with corresponding improvement in C/N ratio.
At a center frequency of 3.95gHz, a relatively flat-topped 121~
(less than +1dB ripple), steep-skirted signal pattern can be achieved utilizing a feedhorn incorporating a circular waveguide having an in-side diameter of approximately 2.4~" and a protrusion of approximately O~9i'. For suc~ configuration, dimension 16 of annular iris 10 is approximately 2.25" and dimension 14 is approximate~y 0.2", or about 1~20 to 1/10 wavelength. Such a feedhorn is optimized for operation with a parabolic reflector having f/D equal to 0.3.
Employing the principles of the present invention, annular irises can be designed to optimize feedhorn performance for parabolic reflectors having f/D ratios ranging from 0.5 down to 0.3. Substan-tial improvement in C/N ratio, on the order of 0.3 dB, is achievable by utilizing the shorter f/D reflector. Such improvement in C/N
ratio is directly attributab~e to the lower noise introduced into the system by the antenna system since the beamwidth pattern of the signal illuminating the parabolic reflector is wider and has steeper skirts than previously achievable.
Protrusion of the aperture can be achieved more than one way. Corrugated plate 22 can be movably mounted (not shown) on cir-cular waveguide 21 so that its distance from the aperture of the P~feedhorn can be varied simply by moving the ~e~lcr along the circular waveguide as required. Conversely, corrugated plate 22 can be fixedly mounted or constructed as part of circular waveguide 21 with i ttle or no protrusion at 24. In that configuration, protrusion dimension 30 would be primarily determined by dimension 14 of annular iris 10 which can be any amount necessary to achieve the desired performance characteristics at a given center frequency. For the l o ~-z~
configuration where protrusion dimension 30 is determined primarily by insertion of annular iris 10, the extent of inside diameter 13 in parallel with the the longitudinal axis of annular iris 10 may become significant. As mentioned el~ewhere in this specification, impedance match of the feedhorn deteriorates as the amount of reduced diameter of the circular waveguide alog its length increases. Thus, the length of diameter 13 may beccme significant as dimension 14 increases.
beamwidth for uniform illumination of the parabolic reflector and steep side skirts of the emitted signal pattern is requiredto meet improved amplifier performance. The ideal signal pattern is flat-topped, having infinitely steep skirts. Furthermore, the pattern should be approximately equal (symmetrical) in the E and H planes which are orthogonal to each other.
E and H plane symmetry is desirable because most communi-cations satellites in use today emit two ort.hogonal signals which must be received. To achieve E and H plane symmetry the aperture of the feedhorn in the E plane should be smaller than that in the H
plane. This corfiguration arises because the electric ~ield of the H
plane is sinusoidally distributed across the diameter of the waveguide and there i~ no curren~-in the sidewalls of the waveguide.
However, the electric field of the E plane causes current to flow in the sidewalls of the waveguide which, upon reaching the aperture, flows down the outside of the waveguide and makes the aperture appear larger. Thus, by reducing the E plane dimension appropriately, the critically equivalent apertur~s for approximately equal E and H plane beamwidths are produced.
A circular waveguid~ is used in most present-day feedhorns because it is the most convenient way to receive the two orthogonal signals transmitted by communications satellites, However, obviously it is not possible to reduce only E plane beamwidths by reducing the aperture of a circular waveguide in one dimension without simulta-neously affecting the other dimension which affects H plane beam-width.
It is well understoc~ that signal beamwidth can be con-trolled by changing aperture size. The smaller the aperture, the wider the pattern for both the E and ~ plane beamwidths. It is also well understood that beamwidth can be controlled by adding a plzte around the aperture of the circular waveguide of the feedhorn, such plates having various configurations, sizes and location behind the aperture. Depending on location, the aperture of the circular wave-guide appears to protrude beyond the plane of the plate~
Location of the plate with respect to the aperture primarily affects the E plane beamwidth since it is interacts with the current flowing down the outside of the waveguide. When the current reaches the plate, it is reflected back toward the aperture.
If that current is at the proper amplitude and in the proper phase when re-introduced at the aperture, it augments the signal pattern emitted by the feedhorn. An equivalent explanation found in the literature refers to excitation of higher order modes which reinforce the principal TE11 mode in the waveguide.
If tho diameter of the aperture of the circular waveguide is reduced by decreasing the diameter of the wavesuide along its entire length, severe impedance mismatch is produced. To overcome that impedance mismatch at the center frequency of interest, the circular waveguide must be lengthened substantially. The longer the waveguide, the more unwieldy th~ feedhorn is to mount, rotate or otherwise conveniently use. According to the present invention, however, E plane signal beamwidth can be controlled by reducing the diameter of the circular waveguide just at the aperture by insertion 5 ~ u of a small annular iris. Impedence match of the feedhorn is thus only slightly compromised.
In practice, location of the plate around the aperture affects both the E and H plane signal patterns. The effect is greater for the E plane than for the H plane, which is expected because of the E
plane current flowing in the walls of the waveguide.
A feedhorn constructed in accordance with the principles of the present invention comprises a circular waveguide having a corrugated plate disposed around the outside of the aperture of the waveguide wherein the corrugations of the plate are capacitive as to E plane signals. In addition, the feedhorn of the present invention includes a reduced aperture diameter which selectively protrudes beyond the plane of the corrugated plate. The amount of protrusion of the aperture is determined to approximately equalize E and H plane beamwidths and selectively shape the top and skirts of signal pattern around the center frequency of interest. Aperture diameter is reduced primarily to control beamwidth for uniform illumination across the entire area of the parabolic reflector.
Various aspects of the invention are as follows:
Apparatus for optimizing performance of a feedhorn with a parabolic reflector in an antenna system, said feedhorn including a circular waveguide for receiving polarized sig~als at an aperture end, impedance matching means coupled to the other end and a corrugated plate disposed around the outside of the circular waveguide near the aperture end, said apparatus comprising an annular iris having an outside diameter approximately equal to the inside diameter of the circular waveguide for interference fit therewith, having an inside diameter determined by the desired beamwidth of the signal to be emitted therefrom, and having a longitudinal dimension selected to protrude beyond the corrugated plate of the feedhorn to approximately equalize the E and H plane beamwidths and selectively shape the signal patterns thereof.
~L6~
5a Method for optimizing performance of a feedhorn ~ith a parabolic reflector in an antenna system, said feedhorn including a circular waveguide for receiving polarized signals at an aperture end, impedance matchin~ means coupled to the other end and a corrugated plate disposed around the outside of the c.ircular waveguide near the aperture end, said method comprising the steps of:
reducing the inside diameter of the aperture end of said circular waveguide of the feedhorn;
protrudirg the aperture end of said circular waveguide of the feedhorn beyond the corrugated plate in an amount equal to that required to approximately equalize the E and H plane beamwidths and selectively shape the signal patterns thereof.
A prime focus feedhorn comprising:
a circular waveguide, having a rear end, an aperture end, and an inside diameter, for receiving polarized signals at the aperture end;
impedance matching means coupled to the rear end for transmitting received signals; and a plate disposed around the outside of 'he circular waveguide near the aperture end havlng corrugations formed by rings thereon concentric with the aperture end;
said aperture end having a diameter selectively less than the inside diameter of the circular waveguide and selectively protruding beyond the plate.
Description of the Drawing Figure lA is a top view of the annular iris constructed according to the principles of the present in~ention.
Figure lB is a sectional view at A-A of the annular iris of Figure lA.
Figure 2 is an exploded sideview of ~ feedhorn incorporating a corrugated plate and the annular iris of Figures lA
6 ~ $V
and ~ according to the present invention.
b~
Figure 3A-D is a graph of the effect on E and H field b ~ -width as a function of aperture protrusion beyond the corrugated plate of prime focus feedhorns including the feedhorn of the present invention incorporating the annular iris of Figures 1A and 1~.
Description of the Preferred Embodiment Referring to Figures 1A and 1B, annular iris 10 according to the preferred embodiment of the present invention is shown having outside diameter 16 inside diameter 12 at its aperture end and longitudinal dimension 14. Inside diameter 13, which is larger than aperture diameter 12 and smaller than outside diameter 16~ can be equal to aperture diameter 1Z for small values of longitudinal dimension 14.
Referring now to Figure 2, outside diameter 16 of annular iris 10 is slightly less than the inside diameter of the circular waveguide )ortion of prime focua feedhorn 20 to provide interference fit as -ri~ 10 is inserted therein. While the interference fit may be sufficient to affix iris 10 to circular waveguide 21, it may be necessary to secure it by using conductive glue, solder, braze or other means for assuring attachment.
Annular iris 10 and feedhorn 20 are both made of aluminum or other suitable materidl which can withstand environmental conditions likely to be encountered and provide the electrical compatibility with the system. While not required, annular iris 10 and feedhorn 20 should be constructed of the same material to avoid 7 ~Z~5~
electrical and electrochemical incompatibilities which may arise from using two different materials. It should be noted that termination of feedhorn 20 at the other end of circular waveguide 21 is not shown, since it is not within the scope of this invention.
Corrugated plate 22 includes corrugaticns formed by rings concentric with aperture 24, shown typically at 25. Preferably, the corrugations are greater than 1/4 wavelength in depth and there are at least 3 of them. By constructing the corrugations deeper than 1~4 wavelength, typically 5/8 wavelength or more, a capacitive reactance is presented to E-plane current flowing on the outside of the feedhorn walls. In addition, the frequency response of feedhorn 20 is approximately flat, less than +1dB, over a broad range of frequencies, e.g. +0.5gHz, around the center frequency of interest.
Thus, the performance of the feedhorn of the present invention is essentially frequency independent around its center frequency.
Dimension 30 refers to the amount in inches of aperture prctrusion beyond corrugated plate 22. Feedhorn 20 may include some fixed aperture protrusion such as that shown at 24. Additional pro-trusion, making up the total protrusion for the feedhorn, is provided by iris 10 and amounts to slightly less than dimension 14, since some of that dimension is consumed when iris 10 is inserted into feedhorn 20 at its aperture 240 Dimension 12 of annular iris 10 affects both E and H plane beamwidth. As stated in this specification, the effect is greater for the E plane pattern. Thus, as dimension 12 is reduced for a given center frequency, E plane beamwidth approaches H plane beamwid'h. 1 2 1 ~ ~tn ~
As protrusion 30 of feedhorn 20 becomes greater, the shape of the E plane signal pattern changes, having steeper skirts and a flatter top, as shown by the three E plane patterns inset above curves 31 and 33 in Figure 3D. The progressive flattening and rippling of the top of a gradually widening E plane pattern in Figures 3A through 3C as aperture protrusion increases is caused by the change in interaction of the re-introduced E plane current with the primary signal at the aperture of the feedhorn. The behavior of H plane pattern is similar, but never becomes as flat on top a~ the wider beamwidths. The Y-axes of Figures 3A-C are in units of dB and the X-axes are in units of angular degrees.
Referring again to Figure 3D, the intersection of curves 31 and 33 indicates approxlmately equalized E and H plane patterns are obtained for a beamwidth of 130 (0.36 f/D reflector) with an aper-ture protrusion of about 0.6". The effect of the present i,vention, selectively reducing the aperture diameter and protruding it beyond a plate having capacitive corrugations, is to shift the intersection of curves 31 and 33 so that approximately equalized E and H plane pat-terns are obtained for a beamwidth of 160 (0.3 ftD reflector) with an aperture protrusion of about 0.9". The improvement of system per-formance in a system utilizing a feedhorn according to the present inventiot. with an 0.3 f/D reflector is reduced electrical noise~
including such noise radiated from thermal sources, introduced into the system with corresponding improvement in C/N ratio.
At a center frequency of 3.95gHz, a relatively flat-topped 121~
(less than +1dB ripple), steep-skirted signal pattern can be achieved utilizing a feedhorn incorporating a circular waveguide having an in-side diameter of approximately 2.4~" and a protrusion of approximately O~9i'. For suc~ configuration, dimension 16 of annular iris 10 is approximately 2.25" and dimension 14 is approximate~y 0.2", or about 1~20 to 1/10 wavelength. Such a feedhorn is optimized for operation with a parabolic reflector having f/D equal to 0.3.
Employing the principles of the present invention, annular irises can be designed to optimize feedhorn performance for parabolic reflectors having f/D ratios ranging from 0.5 down to 0.3. Substan-tial improvement in C/N ratio, on the order of 0.3 dB, is achievable by utilizing the shorter f/D reflector. Such improvement in C/N
ratio is directly attributab~e to the lower noise introduced into the system by the antenna system since the beamwidth pattern of the signal illuminating the parabolic reflector is wider and has steeper skirts than previously achievable.
Protrusion of the aperture can be achieved more than one way. Corrugated plate 22 can be movably mounted (not shown) on cir-cular waveguide 21 so that its distance from the aperture of the P~feedhorn can be varied simply by moving the ~e~lcr along the circular waveguide as required. Conversely, corrugated plate 22 can be fixedly mounted or constructed as part of circular waveguide 21 with i ttle or no protrusion at 24. In that configuration, protrusion dimension 30 would be primarily determined by dimension 14 of annular iris 10 which can be any amount necessary to achieve the desired performance characteristics at a given center frequency. For the l o ~-z~
configuration where protrusion dimension 30 is determined primarily by insertion of annular iris 10, the extent of inside diameter 13 in parallel with the the longitudinal axis of annular iris 10 may become significant. As mentioned el~ewhere in this specification, impedance match of the feedhorn deteriorates as the amount of reduced diameter of the circular waveguide alog its length increases. Thus, the length of diameter 13 may beccme significant as dimension 14 increases.
Claims (3)
1. Apparatus for optimizing performance of a feedhorn with a parabolic reflector in an antenna system, said feedhorn including a circular waveguide for receiving polarized signals at an aperture end, impedance matching means coupled to the other end and a corrugated plate disposed around the outside of the circular waveguide near the aperture end, said apparatus comprising an annular iris having an outside diameter approximately equal to the inside diameter of the circular waveguide for interference fit therewith, having an inside diameter determined by the desired beamwidth of the signal to be emitted therefrom, and having a longitudinal dimension selected to protrude beyond the corrugated plate of the feedhorn to approximately equalize the E and H plane beamwidths and selectively shape the signal patterns thereof.
2. Method for optimizing performance of a feedhorn with a parabolic reflector in an antenna system, said feedhorn including a circular waveguide for receiving polarized signals at an aperture end, impedance matching means coupled to the other end and a corrugated plate disposed around the outside of the circular waveguide near the aperture end, said method comprising the steps of:
reducing the inside diameter of the aperture end of said circular waveguide of the feedhorn;
protruding the aperture end of said circular waveguide of the feedhorn beyond the corrugated plate in an amount equal to that required to approximately equalize the E and H plane beamwidths and selectively shape the signal patterns thereof.
reducing the inside diameter of the aperture end of said circular waveguide of the feedhorn;
protruding the aperture end of said circular waveguide of the feedhorn beyond the corrugated plate in an amount equal to that required to approximately equalize the E and H plane beamwidths and selectively shape the signal patterns thereof.
3. A prime focus feedhorn comprising:
a circular waveguide, having a rear end, an aperture end, and an inside diameter, for receiving polarized signals at the aper-ture end;
impedance matching means coupled to the rear end for trans-mitting received signals; and a plate disposed around the outside of the circular wave-guide near the aperture end having corrugations formed by rings thereon concentric with the aperture end;
said aperture end having a diameter selectively less than the inside diameter of the circular waveguide and selectively protru-ding beyond the plate.
a circular waveguide, having a rear end, an aperture end, and an inside diameter, for receiving polarized signals at the aper-ture end;
impedance matching means coupled to the rear end for trans-mitting received signals; and a plate disposed around the outside of the circular wave-guide near the aperture end having corrugations formed by rings thereon concentric with the aperture end;
said aperture end having a diameter selectively less than the inside diameter of the circular waveguide and selectively protru-ding beyond the plate.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US06/506,494 US4578681A (en) | 1983-06-21 | 1983-06-21 | Method and apparatus for optimizing feedhorn performance |
| US506,494 | 1983-06-21 |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CA1216060A true CA1216060A (en) | 1986-12-30 |
Family
ID=24014831
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA000447751A Expired CA1216060A (en) | 1983-06-21 | 1984-02-17 | Method and apparatus for optimizing feedhorn performance |
Country Status (2)
| Country | Link |
|---|---|
| US (1) | US4578681A (en) |
| CA (1) | CA1216060A (en) |
Families Citing this family (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US4755828A (en) * | 1984-06-15 | 1988-07-05 | Fay Grim | Polarized signal receiver waveguides and probe |
| US4885593A (en) * | 1986-09-18 | 1989-12-05 | Scientific-Atlanta, Inc. | Feeds for compact ranges |
| FR2607968B1 (en) * | 1986-12-09 | 1989-02-03 | Alcatel Thomson Faisceaux | SOURCE OF ILLUMINATION FOR TELECOMMUNICATIONS ANTENNA |
| DE3716033A1 (en) * | 1987-05-14 | 1988-12-01 | Ant Nachrichtentech | DIRECTIONAL ANTENNA |
| US5109232A (en) * | 1990-02-20 | 1992-04-28 | Andrew Corporation | Dual frequency antenna feed with apertured channel |
| US5248987A (en) * | 1991-12-31 | 1993-09-28 | Massachusetts Institute Of Technology | Widebeam antenna |
| US5963176A (en) * | 1997-04-14 | 1999-10-05 | The United States As Represented By The Secretary Of Commerce | Antenna system with edge treatment means for diminishing antenna transmitting and receiving diffraction, sidelobes, and clutter |
| US8872714B2 (en) | 2012-05-17 | 2014-10-28 | Space Systems/Loral, Llc | Wide beam antenna |
| CN105896089B (en) * | 2015-01-23 | 2019-12-10 | 北京空间飞行器总体设计部 | Integrated circularly polarized antenna |
Family Cites Families (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| GB708614A (en) * | 1951-08-31 | 1954-05-05 | Ericsson Telefon Ab L M | Microwave antenna |
| US3434146A (en) * | 1966-08-03 | 1969-03-18 | Us Army | Low profile open-ended waveguide antenna with dielectric disc lens |
| US3553707A (en) * | 1967-05-25 | 1971-01-05 | Andrew Corp | Wide-beam horn feed for parabolic antennas |
| US3815139A (en) * | 1973-04-16 | 1974-06-04 | Prodelin Inc | Feed horns for reflector dishes |
| US4338609A (en) * | 1980-12-15 | 1982-07-06 | Rca Corporation | Short horn radiator assembly |
-
1983
- 1983-06-21 US US06/506,494 patent/US4578681A/en not_active Expired - Lifetime
-
1984
- 1984-02-17 CA CA000447751A patent/CA1216060A/en not_active Expired
Also Published As
| Publication number | Publication date |
|---|---|
| US4578681A (en) | 1986-03-25 |
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