EP2140643A1 - Digital radio system and method of operation - Google Patents
Digital radio system and method of operationInfo
- Publication number
- EP2140643A1 EP2140643A1 EP08732809A EP08732809A EP2140643A1 EP 2140643 A1 EP2140643 A1 EP 2140643A1 EP 08732809 A EP08732809 A EP 08732809A EP 08732809 A EP08732809 A EP 08732809A EP 2140643 A1 EP2140643 A1 EP 2140643A1
- Authority
- EP
- European Patent Office
- Prior art keywords
- frequency
- signal
- digital
- sampling
- radio
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Ceased
Links
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/06—Receivers
- H04B1/16—Circuits
- H04B1/26—Circuits for superheterodyne receivers
- H04B1/28—Circuits for superheterodyne receivers the receiver comprising at least one semiconductor device having three or more electrodes
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
- H04B1/40—Circuits
- H04B1/403—Circuits using the same oscillator for generating both the transmitter frequency and the receiver local oscillator frequency
- H04B1/406—Circuits using the same oscillator for generating both the transmitter frequency and the receiver local oscillator frequency with more than one transmission mode, e.g. analog and digital modes
Definitions
- This invention relates in general to signal processing, and more particularly to a digital radio system.
- a digital radio system comprises a mixer and an analog-to-digital converter communicatively coupled to the mixer.
- the mixer generates an intermediate frequency signal based at least in part upon a radio frequency signal and a local oscillator signal, wherein the intermediate frequency signal comprises a signal of interest having a particular bandwidth.
- the analog-to-digital converter generates a digital signal by quantizing the intermediate frequency signal using a sampling frequency that is greater than twice the bandwidth of the signal of interest and less than the frequency of the intermediate frequency signal.
- Another embodiment of the present invention is a method for tuning a frequency signal.
- the method starts by generating an intermediate frequency signal based at least in part upon a radio frequency signal and a local oscillator signal, wherein the intermediate frequency signal comprises a signal of interest having a particular bandwidth.
- the method concludes by generating a digital signal by quantizing the intermediate frequency signal using a sampling frequency that is greater than twice the bandwidth of the signal of interest and less than the frequency of the intermediate frequency signal.
- the tuner of the digital radio system adopts a particular sampling approach when digitizing the intermediate frequency signal.
- the analog-to-digital converter quantizes the intermediate frequency signal using a sampling frequency that is greater than twice the bandwidth of the signal of interest and less than the frequency of the intermediate frequency signal.
- a result, in one embodiment, is that the frequency of the digital signal is one quarter of the sampling frequency.
- the sampling frequency is selected in such a way that the subsequent baseband conversion can be realized without complex frequency mixing.
- the baseband conversion can be achieved with simple multiplication (e.g., for I: 1, -1, -1, and 1; and for Q: 1, 1, -1, -1 ; or, alternatively, for I: 1, 0, -1, and 0; and for Q: 0, 1, 0, and -1), thereby reducing the computing power necessary in the digital signal processing (DSP) circuitry.
- the data rate is an integer multiple of standard audio sample rates like 48 kHz or 44.1 kHz, which reduces the necessary computing power even further. This results in power savings in the DSP and enables implementation of an AM/FM/WX radio using an "off the shelf DSP.
- FIGURE 1 illustrates a simplified block diagram of a digital radio system according to the present invention
- FIGURE 2 illustrates a series of frequency graphs depicting the digitization of a radio frequency signal in the system of FIGURE 1 ;
- FIGURE 3 illustrates several embodiments of frequency schemes that can be used in the system of FIGURE 1 ;
- FIGURE 4 illustrates a more detailed embodiment of a digital radio system according to the present invention.
- FIGURE 1 illustrates a simplified block diagram of a digital radio system 10 comprising a tuner block 12 and a digital signal processing (DSP) block 14.
- Tuner block 12 comprises a mixer 18 and an analog-to-digital converter (ADC) 20.
- DSP block 14 comprises a mixer 22.
- the digitization performed by ADC 20 is performed using a bandpass sampling approach so that the subsequent baseband conversion performed by DSP block 14 can be performed on the digital signal without the need for complex frequency mixing.
- an AM/FM/WX radio can be implemented using an "off the shelf digital signal processing circuit.
- a mixer comprises a circuit element that performs frequency translation of a broadband signal to an intermediate frequency (IF) signal, or from an IF signal to a baseband signal, or from a broadband signal to a baseband signal.
- a mixer may comprise a bolometer, photoconductor, Schottky diode, quantum nonlinear device (e.g. SIS receiver or Josephson junction mixer), variable gain amplifier, or any other suitable device that multiplies a first frequency signal with a local oscillator (LO) signal to generate a second frequency signal.
- LO local oscillator
- Mixer 18 multiplies at least a portion of RF signal 30 with an LO signal 32 to generate an IF signal 34.
- mixer 18 comprises an image rejection mixer that eliminates image noise from an unwanted sideband of IF signal 34.
- RF signal 30 may comprise an FM signal 30a, an AM signal 30b, a WX signal 30c, or any other suitable radio frequency signal whether or not illustrated herein.
- An FM signal 30a generally comprises a radio frequency signal within the FM radio band that ranges from 65 to 108 MHz.
- Each FM signal 30a generally has up to a 200 kHz bandwidth that includes the center frequency and the upper and lower guard bands.
- an FM signal 30a has up to a 400 kHz bandwidth in order to include high definition content.
- An AM signal 30b generally comprises a radio frequency signal within the AM radio band that ranges from 144 to 26100 kHz.
- Each AM signal 30b generally has up to a 10 kHz bandwidth. In some embodiments, an AM signal 30b has up to a 40 kHz bandwidth in order to include high definition content.
- a WX signal 30c generally comprises a radio frequency signal within the weather band that ranges from 162.400 MHz to 162.550 MHz. Each WX signal 30c generally has up to a 25 kHz bandwidth.
- RF signal 30 includes a signal of interest 36 having an appropriate bandwidth depending on whether the signal 36 is within the FM, AM or WX band, as described above.
- Mixer 16 generates IF signal 34 based on signal 36 and an appropriate LO signal 32.
- Particular embodiments of system 10 are operated to generate IF signal 34 at a frequency of: (a) 10.7 MHz; (b) 12.0 MHz; or (c) 11.025 MHz, as described in greater detail below. These embodiments illustrate example frequencies, but it should be understood that any suitable frequency for IF signal 34 may be used.
- LO signal 32 is selected to frequency convert signal 36 to the selected frequency for IF signal 34.
- ADC 20 comprises any suitable electronic circuit that converts an analog signal, such as IF signal 34, into a digital signal, such as digital signal 40.
- the sampling frequency of ADC 20, f s is selected to be greater than twice the bandwidth of the signal of interest 36, and less than the frequency of IF signal 34.
- This bandpass sampling approach is based on folding signal 34 in a Nyquist Zone that is two or higher in order to generate a digital signal 40 that is well suited for subsequent digital signal processing, such as audio processing, channel coding, weak- signal processing, and so forth.
- the bandpass sampling approach of system 10 is a departure from traditional sampling techniques that rely upon the Nyquist-Shannon theorem whereby the sampling frequency used to acquire a signal is at least twice the signal's highest frequency component.
- the bandpass sampling approach of system 10 takes advantage of the fact that the bandwidth of the signal of interest in an AM/FM/WX radio system is much smaller than the highest frequency component.
- the sampling frequency of ADC 20 is selected according to the following formula:
- f s sampling frequency of ADC 20
- fip frequency of IF signal 34
- the frequency of digital signal 40 is given by the following formula:
- the frequency of digital signal 40 equals one quarter of the sampling frequency of ADC 20.
- digital signal 40 is presented to DSP block 14 in such a way that the subsequent baseband conversion can be realized without complex frequency mixing.
- mixer 22 of DSP block 14 can perform a baseband conversion of digital signal 40 by multiplying digital signal 40 with an LO signal 42 that isf s / 4.
- LO signal 42 can be generated using a cosine wave (e.g., 1, -1, -1, and 1; or 1, 0, -1, and 0 to generate the I signal) or a sin wave (e.g., 1, 1, -1, and -1; or 0, 1, 0, and -1 to generate the Q signal).
- a cosine wave e.g., 1, -1, -1, and 1; or 1, 0, -1, and 0 to generate the I signal
- a sin wave e.g., 1, 1, -1, and -1; or 0, 1, 0, and -1 to generate the Q signal.
- ADC 20 is detailed with reference to digitizing an IF signal 34, it should be understood that the bandpass sampling approach set forth above can be implemented to digitize an RF signal 30 without departing from the scope of the present disclosure. This can be done by substituting the frequency of the RF signal 30 in the formulas 1 and 2 above where the frequency of the IF signal 34 was used.
- Nyquist Zones discussed above can be determined according to the sampling frequency, ⁇ .
- Nyquist Zone 1 comprises frequencies between 0 and f s I 2.
- Nyquist Zone 2 comprises frequencies between /J / 2 and f s .
- Nyquist Zone 3 comprises frequencies between f s and 2>f s 1 2.
- the remaining Nyquist Zones 4- 13 can be defined similarly.
- FIGURE 2 illustrates a series of frequency graphs 50a, 50b, and 50c depicting the digitization of an RF signal 30 according to the present invention.
- one of RF signals 30a, 30b, 30c of graph 50a is frequency converted to IF signal 34 of graph 50b using mixer 18.
- signals 30a, 30b, and 30c represent an FM band, an AM band, and a weather band, respectively.
- signals 30a (FM band) and 30c (WX band) are down-converted to IF signal 34.
- Signal 30b (AM band) may be up-converted or down-converted to IF signal 34 depending on the frequency of the particular signal of interest 36 within the AM band.
- the frequency of IF signal 34 is 12.0 MHz.
- IF signal 34 of graph 50b is quantized to generate digital signal 40 using ADC 20 operating at the sampling frequency determined above, for example, using formula 1.
- the sampling frequency of ADC 20 that is used is 1.920 MHz.
- the frequency of the resulting digital signal 40 is .480 MHz, which equalss / 4.
- FIGURE 3 illustrates frequency schemes 60a, 60b, and 60c that can be used in system 10.
- frequency scheme 60a is based upon generating an IF signal 34 of 10.7 MHz;
- frequency scheme 60b is based upon using a 48 kHz audio sample rate;
- frequency scheme 60c is based upon using a 44.1 kHz audio sample rate.
- each of these frequency schemes 60 includes an appropriate frequency for IF signal 34 in row 62a, sampling frequency of ADC 20 in row 62b, and frequency of digital signal 40 in row 62c. These frequencies are determined using the formulas 1 and 2 above. Using one of these frequency schemes 60a-c allows radio system 10 to use standard components for tuner block 12 and/or DSP block 14.
- FIGURE 4 illustrates a more detailed embodiment of a digital radio system
- System 100 having a tuner block 12 and a DSP block 14, according to the present invention.
- System 100 comprises antennas 102a and 102b to receive RF signals 30a and 30b.
- Impedance matching elements 104a and 104b match the different impedances of the antennas 102a and 102b to the low noise amplifiers 116a and 116b.
- Attenuators 106a and 106b attenuate the respective signals 30a and 30b provided by antennas 102a and 102b to avoid overloading the remainder of tuner block 12.
- attenuators 106a and 106b comprise PIN-diodes that operate in conjunction with respective automatic gain control elements 108a and 108b.
- a first tracking filter 1 10 and a second tracking filter 112 perform filtering on RF signal 30a in the FM band in order to provide the signal of interest 36.
- tracking filters 110 and 112 facilitate providing a signal that is 2-4 MHz wide and that contains the signal of interest 36.
- Tracking filters 110 and 1 12 operate in response to signals received by a tuning capacitor 114.
- An LNA 116a amplifies signal of interest 36 in conjunction with the automatic gain control element 108a for provisioning to the image rejection mixer 18 through the bandswitch 120.
- Band filter 118 provides a signal of interest 36 from an RF signal 30b in the AM band.
- the bandswitch 120 allows the tuner block 12 of system 100 to be implemented using only one mixer 18 for use with both the FM band and the AM band.
- Mixer 18 generates IF signal 34, as described above with reference to FIGURES 1 and 2, in conjunction with the VCO 112, loop filter 124, fraction-n- PLL 126, and reference oscillator 128.
- IF signal 34 may be processed by one or more channel filters 140, 142, 144, and 146 in order to provide steep selectivity and a narrow bandwidth around the signal of interest 36 prior to performing the analog-to-digital processing.
- the number and combination of channel filters 14-146 used in tuner block 12 is customizable and specific to a particular application.
- the IBOC channel filters 142 and 146 refer to an "in-band-on-channel" filter and is used for high definition radio applications.
- a variable gain amplifier 150 adjusts the filtered IF signal 34 to prepare it suitably for the subsequent analog-to-digital processing.
- Amplifier 150 operates in response to control signals 152.
- a noise filter 154 is implemented prior to the ADC 20 in order to clean up IF signal 34 prior to digitization in order to resolve any noise folding problems that may arise due to the bandpass sampling approach implemented by ADC 20.
- ADC 20 digitizes IF signal 34 to create digital signal 40 according to the bandpass sampling approach described above.
- Digital signal processing element 160 comprises any suitable DSP chip or other circuitry designed to perform digital signal processing. In one embodiment, such a DSP chip may be a standard, "off the shelf DSP chip.
- tuner 12 Various elements of the tuner 12 are implemented on an integrated circuit that is illustrated using dashed lines 130.
- a particular novelty associated with system 100 is that mixer 18 and ADC 20 reside on the same integrated circuit.
- tuning capacitor 114 also resides on the same integrated circuit as mixer 18 and ADC 20.
Abstract
Description
Claims
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US11/693,876 US7446692B2 (en) | 2007-03-30 | 2007-03-30 | Digital radio system and method of operation |
PCT/US2008/058170 WO2008121627A1 (en) | 2007-03-30 | 2008-03-26 | Digital radio system and method of operation |
Publications (1)
Publication Number | Publication Date |
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EP2140643A1 true EP2140643A1 (en) | 2010-01-06 |
Family
ID=39494211
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
EP08732809A Ceased EP2140643A1 (en) | 2007-03-30 | 2008-03-26 | Digital radio system and method of operation |
Country Status (4)
Country | Link |
---|---|
US (2) | US7446692B2 (en) |
EP (1) | EP2140643A1 (en) |
TW (1) | TW200901698A (en) |
WO (1) | WO2008121627A1 (en) |
Families Citing this family (11)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US7446692B2 (en) * | 2007-03-30 | 2008-11-04 | Microtune (Texas), L.P. | Digital radio system and method of operation |
JP2009171349A (en) * | 2008-01-17 | 2009-07-30 | Nsc Co Ltd | Receiver |
US8401600B1 (en) | 2010-08-02 | 2013-03-19 | Hypres, Inc. | Superconducting multi-bit digital mixer |
US8525717B2 (en) * | 2010-08-13 | 2013-09-03 | Rf Micro Devices, Inc. | Half-bandwidth based quadrature analog-to-digital converter |
US8542775B2 (en) | 2010-11-12 | 2013-09-24 | Csr Technology Inc. | Serial data interface for software-defined radio system |
CN102694615A (en) * | 2011-03-21 | 2012-09-26 | 英华达(上海)科技有限公司 | Digital radio frequency modulation device |
US8717212B2 (en) * | 2012-09-20 | 2014-05-06 | Phuong Huynh | Bandpass-sampling delta-sigma demodulator |
TWI489796B (en) * | 2013-11-14 | 2015-06-21 | Realtek Semiconductor Corp | Wireless signal receiving device and method |
CN106998209B (en) * | 2013-11-19 | 2019-08-23 | 瑞昱半导体股份有限公司 | Wireless signal receiver and method |
US9461588B1 (en) * | 2015-06-09 | 2016-10-04 | Microsoft Technology Licensing, Llc | Doubly balanced josephson junction mixer |
CN105227197B (en) * | 2015-10-19 | 2017-07-07 | 中国电子科技集团公司第二十八研究所 | A kind of quick frequency locking method of reseptance of X-band |
Family Cites Families (9)
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FR2702902B1 (en) * | 1993-03-15 | 1995-04-21 | Alcatel Radiotelephone | Digital intermediate frequency receiver and baseband filtering method implemented in this receiver. |
US6714608B1 (en) | 1998-01-27 | 2004-03-30 | Broadcom Corporation | Multi-mode variable rate digital satellite receiver |
DE69908577T2 (en) * | 1999-06-30 | 2003-12-11 | Motorola Inc | Apparatus and method for receiving and processing a radio frequency signal |
US6922555B1 (en) * | 1999-09-02 | 2005-07-26 | Koninklijke Philips Electronics N.V. | Phase interpolation receiver for angle modulated RF signals |
US6553215B1 (en) | 2000-07-27 | 2003-04-22 | Kim-Por Chung | Weather radio control |
US7010443B2 (en) * | 2003-10-31 | 2006-03-07 | Agilent Technologies, Inc. | Noise measurement system and method |
US7272373B2 (en) | 2004-06-30 | 2007-09-18 | Silacon Laboratories Inc. | Ratiometric clock systems for integrated receivers and associated methods |
US7978643B2 (en) * | 2005-05-17 | 2011-07-12 | Nokia Corporation | Dynamic adjustment of multiple reception paths |
US7446692B2 (en) | 2007-03-30 | 2008-11-04 | Microtune (Texas), L.P. | Digital radio system and method of operation |
-
2007
- 2007-03-30 US US11/693,876 patent/US7446692B2/en active Active
-
2008
- 2008-03-26 EP EP08732809A patent/EP2140643A1/en not_active Ceased
- 2008-03-26 WO PCT/US2008/058170 patent/WO2008121627A1/en active Application Filing
- 2008-03-28 TW TW097111353A patent/TW200901698A/en unknown
- 2008-11-03 US US12/263,906 patent/US7852251B2/en active Active
Non-Patent Citations (2)
Title |
---|
CHANG-GENE WOO ET AL: "Relationship between ADC performance and requirements of digital-IF receiver for WCDMA base-station", IEEE TRANSACTIONS ON VEHICULAR TECHNOLOGY, IEEE SERVICE CENTER, PISCATAWAY, NJ, US, vol. 52, no. 5, 1 September 2003 (2003-09-01), pages 1398 - 1408, XP011101026, ISSN: 0018-9545, DOI: 10.1109/TVT.2003.816621 * |
See also references of WO2008121627A1 * |
Also Published As
Publication number | Publication date |
---|---|
TW200901698A (en) | 2009-01-01 |
US20090058706A1 (en) | 2009-03-05 |
US7852251B2 (en) | 2010-12-14 |
US7446692B2 (en) | 2008-11-04 |
WO2008121627A1 (en) | 2008-10-09 |
US20080238751A1 (en) | 2008-10-02 |
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