|Publication number||US20020067315 A1|
|Application number||US 09/375,319|
|Publication date||Jun 6, 2002|
|Filing date||Aug 16, 1999|
|Priority date||Aug 16, 1999|
|Also published as||DE60006132D1, DE60006132T2, EP1205009A1, EP1205009B1, US6445354, US6452560, US20020011965, WO2001013465A1|
|Publication number||09375319, 375319, US 2002/0067315 A1, US 2002/067315 A1, US 20020067315 A1, US 20020067315A1, US 2002067315 A1, US 2002067315A1, US-A1-20020067315, US-A1-2002067315, US2002/0067315A1, US2002/067315A1, US20020067315 A1, US20020067315A1, US2002067315 A1, US2002067315A1|
|Original Assignee||Waldemar Kunysz|
|Export Citation||BiBTeX, EndNote, RefMan|
|Referenced by (17), Classifications (22), Legal Events (5)|
|External Links: USPTO, USPTO Assignment, Espacenet|
 1. Field of the Invention
 The present invention is related to planar broadband antennas and, more particularly, to an antenna for transmitting or receiving circularly-polarized signals.
 2. Description of the Prior Art
 Antennas producing circularly-polarized signals are known in the art. U.S. Pat. No. 5,861,848, issued to Iwasaki, for example, discloses a circularly polarized wave patch antenna with short circuit portion. The directivity of a patch antenna can be increased by incorporation of a choke ring ground plane, but this increases the weight of the antenna.
 U.S. Pat. No. 5,815,122, issued to Nurnberger et al., for example, discloses a slot spiral antenna with a single spiral slot on one side of the antenna, and a spiral microstrip feed line on the reverse side. The reference teaches primarily a single-slot configuration which results in an antenna having a low directivity. Moreover, the placement of an additional component, such as a low-noise amplifier, on the antenna itself is impractical.
 While the art describes planar antennas producing circularly-polarized radiation, there remains a need for improvements that offer advantages and capabilities not found in presently available devices, and it is a primary object of this invention to provide such improvements. It is another object of the invention to provide such a planar antenna with an improved directivity.
 It is yet another object of the present invention to provide a slot array antenna having a distribution feed line which matches the input/output signals with the spatial angular configuration of the antenna slots.
 It is further another object of the present invention to provide such a planar antenna which allows for the mounting of active circuitry on the antenna substrate.
 Other objects of the invention will be obvious, in part, and, in part, will become apparent when reading the detailed description to follow.
 A planar antenna includes a nonconductive substantially planar substrate and a transmission line disposed on one surface, a segment of the transmission line forming an arc of radius R centered on the antenna axis. A conductive layer on the other antenna surface includes two or more slotted openings, each slotted opening having one end located within a distance R of the antenna axis, such that, when an electromagnetic signal is fed into one end of the transmission line, electromagnetic energy is sequentially coupled into the slotted openings, and a circularly-polarized signal is radiated from the antenna substantially in the direction of the antenna axis. The electrical phase length of the transmission line is matched to the spatial angular difference between two consecutive slotted openings, so as to provide for a phased-array operation.
 An amplifier or a connector may be electrically connected to one or both ends of the transmission line, or one end of the transmission line may be terminated in an impedance load to form a leaky-wave antenna. The slotted openings may comprise either or both straight and curved segments, and may be of the same or unequal lengths. Curved slotted openings may be oriented clockwise or counter-clockwise to transmit or receive either left-handed or right-handed polarized signals.
 The invention description below refers to the accompanying drawings, of which:
FIG. 1 is a diagrammatical view of the back side of an antenna in accordance with the present invention showing an arc-shaped transmission line disposed about an antenna axis;
FIG. 2 is a cross-sectional view of the antenna of FIG. 1 showing a conductive plane disposed on the antenna front side;
FIG. 3 is a diagrammatical view of the front side of the antenna of FIG. 1 showing an array of slotted openings disposed in the conductive plane;
FIG. 4 is an end view of the antenna of FIG. 3 showing the placement of an optional reflector to increase the proportion of electromagnetic energy transmitted in the antenna forward direction;
FIG. 5 is a first embodiment of an antenna including four equal-length slotted openings arrayed at 90° intervals about the antenna axis;
FIG. 6 is a view of the back side of the antenna of FIG. 5 showing an signal amplifier and an impedance load attached to the ends of a transmission line;
FIG. 7 is a second embodiment of an antenna including curved slotted openings with straight radial slotted segments to increase coupling between the slotted openings and a transmission line;
FIG. 8 is a third embodiment of an antenna including clockwise spiral slotted openings of two different lengths for transmitting or receiving left-hand polarized signals of two different wavelengths;
FIG. 9 is a view of the back side of the antenna of FIG. 8 showing a wide transmission line for optimally coupling signals of two different wavelengths;
FIG. 10 is a front view of a fourth embodiment of an antenna with high directivity including twelve spiral-shaped slotted openings equally arrayed about the antenna axis;
FIG. 11 is a front view of a fifth embodiment of an antenna including an array of straight slotted openings; and
FIG. 12 is a rear view of the antenna of FIG. 11 showing low-noise signal amplifiers attached to the ends of a transmission line.
FIG. 1 is a diagrammatical view showing the back side of a substantially planar antenna 10 for receiving or transmitting electromagnetic signals of wavelength λ, in accordance with the present invention. A back surface 13 of the antenna 10 is bounded by a peripheral edge 17. The peripheral edge 17 encloses an antenna axis 11 oriented orthogonal to the back surface 13. A transmission line 21, which may be a microstrip, a coplanar waveguide, or other such conductive component as known in the relevant art, is disposed on the back surface 13. The transmission line 21 includes an input end 23 for receiving or outputting the electromagnetic signals. The input end is electrically connected by a first conductive lead 12 to a connector 22, such as an RF connector, for interfacing with external circuitry. A terminal end 25 of the transmission line 21 is electrically connected to a load impedance 24 via a second conductive lead 14. The transmission line 21 is in the shape of a circular arc, where an inside edge 29 of the transmission line 21 lies at a radius of R and an outside edge 27 lies at a radius of R+w from the antenna axis 11. The guided wave length of the transmission line is equal to one or more transmitted (or received) wavelengths λ.
FIG. 2 is a cross-sectional view of the antenna 10 as indicated by the sectional arrows in FIG. 1. The antenna 10 comprises a substrate 19 of nonconductive or dielectric material having a thickness t, where the transmission line 21 is disposed on the back surface 13 of the substrate 19 and a conductive layer 31 is disposed on a front surface 15 of the substrate 19. The front surface 15 is likewise bounded by the peripheral edge 17.
FIG. 3 is a diagrammatical view of the front side of the antenna 10 showing that the conductive layer 31 includes a plurality of similar curved, slotted openings 33, 35, 37, and 39, where each slotted opening 33, 35, 37, and 39 extends through the conductive layer 31 to the front surface 15 of the substrate 19. The antenna 10 may thus be fabricated from a two-layer printed circuit board (PCB), where the transmission line 21 and the slotted openings 33, 35, 37, and 39 can be formed by suitably etching portions of the respective cladding layers to form the slotted openings 33, 35, 37, and 39 and the transmission line 21. It should be understood that, although four slotted openings are shown for purpose of illustration, the present invention is not limited to this number and may comprise m slotted openings of varying shapes and lengths, where m≧2, as explained in greater detail below.
 Moreover, the slotted openings can be curved in shape as shown, or can be straight segments or a combination of both straight and curved segments, as described in greater detail below. The curved shapes can be a conical section (i.e., a circular, elliptical, parabolic, or hyperbolic arc), an Archimedean spiral, a logarithmic spiral, or an exponential spiral. Straight slotted openings are equivalent to dipoles and, as such, a single slotted opening produces a linearly polarized signal. However, an array of straight slotted openings can be used to transmit, or receive, a circularly-polarized signal, as described in greater detail below. Circular polarization can also be produced by using an array of curved slotted openings, where the respective slotted openings are curved in the direction of the desired circular polarization (i.e., a clockwise curvature to receive or transmit left-hand circularly polarized signals). By using curved slotted openings having the equivalent guided wave lengths of straight slotted openings, the physical size of the antenna can be reduced.
 The slotted openings 33, 35, 37, and 39 have respective axial ends 33 a, 35 a, 37 a, and 39 a proximate the antenna axis 11, and respective peripheral ends 33 p, 35 p, 37 p, and 39 p proximate the peripheral edge 17. Axial ends 33 a, 35 a, 37 a, are, respectively, d1, d2, d3, and d4 from the antenna axis 11 where di<R. That is, the respective axial ends 33 a, 35 a, 37 a, and 39 a of the respective slotted opening 33, 35, 37, and 39 lie inside the circle of radius R defined by the transmission line 21 (here shown in phantom) on the opposite side of the substrate 19. Accordingly, when the antenna 10 is used to transmit signals, electromagnetic energy is fed into the transmission line 21 and is electromagnetically coupled to the slotted opening 33, 35, 37, and 39. This coupling occurs at the four respective regions where the slotted openings 33, 35, 37, and 39 which lie on the front surface 15, are located most proximate to and directly opposite the transmission line 21 which lies on the back surface 13 of the planar antenna 10.
 For example, a portion of the slotted opening 33 is located a distance equivalent to the substrate thickness t from the transmission line 21 at a coupling region 43. As is well known in the relevant art, the electromagnetic energy passing through transmission line 21 will produce a radiating field across the slotted opening 33 in the coupling region 43. This electromagnetic energy will be similarly coupled into slotted openings 35, 37, and 39 at coupling regions 45, 47, and 49 respectively. The degree of coupling is a function of the thickness t of the substrate 19, the width w of the transmission line 21, the width v of the slotted opening 33, and the dielectric properties of the substrate 19. Conversely, when the antenna 10 is used to receive signals, radiation energy is received at the slotted openings 33, 35, 37, and 39 is coupled into the transmission line 21 at the respective coupling regions 43, 45, 47, and 49.
 As can be appreciated by one skilled in the relevant art, electromagnetic energy radiated by the antenna 10 is emitted in both directions along the antenna axis 11. To increase the proportion of energy emitted in the forward direction and reduce the backlobe radiation, a reflector 40 may be emplaced in opposed parallel relationship to the back surface 13 of the antenna 10, as shown in FIG. 4. In an alternative embodiment, an enclosed cavity (not shown) could be used in place of the reflector 40 as is well-known in the relevant art. The radiation pattern emitted from the antenna 10, as well as the radiation pattern roll-off characteristics, can also be varied as desired by increasing or decreasing the separation between the reflector 40 and the antenna 10.
FIG. 5 is the front view of a first embodiment of a planar antenna 50 in accordance with the present invention. The planar antenna 50 includes four similar spiral-shaped slotted openings 53, 55, 57, and 59 each of width v and guided wave length LGW symmetrically arrayed about an antenna axis 51 at angular intervals of
 radians. This configuration provides for a phased-array slot antenna. Since the slotted openings 53, 55, 57, and 59 curve in the counter-clockwise direction, the transmitted or received signals will be right-hand polarized. Conversely, signals having a left-hand polarization are produced (or received) when the slotted openings 53, 55, 57, and 59 are curved in the clockwise direction. Unwanted cross-polarization is minimized by keeping the opening width v narrow in comparison to the guided wave length LGW. The shape of each of the slotted openings 53, 55, 57, and 59 can be described best in polar coordinates using the antenna axis 51 as origin. The radial distances r(θ) of the interior edges of the slotted openings 53, 55, 57, and 59 increase from ra at the respective axial ends 53 a, 55 a, 57 a, and 59 a, to a maximum radius of rp at the respective peripheral ends 53 p, 55 p, 57 p, and 59 p. The radial distance from the antenna axis 51 to the inside edge of any of the slotted opening 53, 55, 57, and 59 increases with the polar angle θ and is also a function of the interval spacing Δr for each spiral-shaped slotted opening where Δr≡r(θ+2π)−r(θ). For the slotted opening 53, the radial distance from the antenna axis 51 can be described by means of the equation,
 The slotted opening 55 is spatially offset from the slotted opening 53 by
 radians (90°). Similarly, the slotted opening 57 is spatially offset by π radians (180°), and the slotted opening 59 is spatially offset by
 The radial distances r(θ,Δr) of the interior edges of the three slotted openings 55, 57, and 59 can thus be determined by the respective equations,
 The guided wave length LGW of each of the slotted openings 53, 55, 57, and 59 is specified to be a multiple of quarter-wavelengths of the receiving or transmitting signal in order to maximize the antenna efficiency
 In the configuration shown, each spiral-shaped slotted opening subtends an angle of θp, where
 The width v of each of the slotted openings 53, 55, 57, and 59 is specified to be substantially smaller than the guided wave length and large enough to enable good electromagnetic coupling between the respective slotted opening 53, 55, 57, and 59 and a transmission line 61, best seen in FIG. 6 which is a rear view of the planar antenna 50. The transmission line 61 “crosses” each of the slotted openings 53, 55, 57, and 59 at respective coupling regions 63, 65, 67, and 69. The coupling regions 63, 65, 67, and 69 are offset by
 radians (90°) from one another. This configuration provides for matching the electrical phase differences in the coupling regions 63, 65, 67, and 69 (i.e., differences of 90°) with the spatial differences of the slotted openings 53, 55, 57, and 59 when the guided wave length of the transmission line 61 is tuned to be one wavelength λ. A single, omnidirectional beam is produced when the guided wave length of the transmission line 61 is one wavelength λ, a squinted beam is produced when the guided wave length is less than one wavelength, and multiple directional beams are produced when the guided wave length of the transmission line 61 is more than one wavelength.
 A signal is transmitted (or received) by means of a signal source (or receiver) connected to an input/output end 62 of the transmission line 61 via a low-noise amplifier 71. A connector 75 provides for connecting the transmitted (or received) signal to external circuitry via a coaxial cable, an optical fiber, or a waveguide. An impedance load 73 is coupled to a terminal end 64 of the transmission line 61 to provide a leaky-wave antenna configuration and to thus ensure a uniform amplitude coupling to all slotted openings 53, 55, 57, and 59. Alternatively, the connector 75 can be directly attached to the input/output end 62 of the transmission line 61 and the amplifier 71 can be located on a separate circuit board.
 For the configuration shown, a transmitted signal originating in the low-noise amplifier 71 and terminating in the impedance load 73 passes through the transmission line 61 in a counter-clockwise direction (as viewed from the front of the planar antenna 50). As the transmitted signal is successively coupled to the slotted openings 53, 55, 57, and 59 at the respective coupling regions 63, 65, 67, and 69, a right-hand polarized signal is emitted from the planar antenna 50. Alternatively, the signal can be transmitted through the transmission line 61 in a clockwise direction and the slotted openings 53, 55, 57, and 59 can be curved in a clockwise direction for a transmitted (or received) signal which is left-hand polarized. For a configuration in which the signal travels in the direction opposite to the direction of the spiral slotted openings, both right-hand and left-hand polarized radiation is transmitted (or received).
 In a second embodiment, shown in FIG. 7, an antenna 80 comprises an array of four slotted openings 81, 83, 85, and 89 coupled to the transmission line 61 (on the back side of the antenna 80). To improve electromagnetic coupling to the transmission line 61, the slotted openings 81, 83, 85, and 87 each include a straight, radial segment 89 oriented at a right angle to the transmission line 61. The slotted openings 81, 83, 85, and 87 together with the respective radial segments 89 are tuned so as to optimally transmit (or receive) a specified wavelength λ. Because slotted antennas are broadband, the antenna 80 can transmit (or receive) a spectral band of wavelengths, in addition to radiation of wavelength λ. If the spectral band of wavelengths lies within 30% of λ, a slotted opening tuned to a guided wave length λ can also be used for transmitting (or receiving) the spectral band wavelengths. For wavelengths lying outside this spectral band, a second slotted opening of different guided wave length is used.
 For example, in the third embodiment shown in FIG. 8, an antenna 90 is configured to transmit and receive left-hand polarized signals at two wavelengths, λ1, and λ2. Two slotted openings 91 and 95 are tuned for the longer wavelength λ1, and two slotted openings 93 and 97 are tuned for the shorter wavelength λ2. The slotted opening 91 can be tuned to the wavelength λ1 by having a guided wave length LGW of: i) one wavelength (λ1), ii) two wavelengths (2λ1), iii) one-half wavelength
 iii) one-quarter wavelength
 or iv) some other multiple or fraction of a wavelength
 The antenna 90 comprises a transmission line 101 having a greater width in comparison to the width of transmission line 61 (in FIG. 6). As best seen in FIG. 9, the transmission line 101 has an inside edge 103 of radius of curvature R1 and an outside edge 105 of radius of curvature R2=R1+w. As well-known in the relevant art, a signal propagating within the transmission line 101 will appear mostly at the edges 103 and 105. The guided wave length along the inside edge 103 is smaller than the guided wave length along the outside edge 105 by the fraction
 By selecting suitable values for R1 and R2, the transmission line 101 can be optimized for coupling more than one wavelength into the array of slotted openings 91, 93, 95, and 97.
 As stated above, the invention is not limited to a single frequency or to only four slotted openings. In a fourth embodiment, shown in FIG. 10, an antenna 110 comprises six slotted openings 111 tuned to a first wavelength λ1, and six slotted openings 113 tuned to a second, shorter wavelength λ2. The array of slotted openings 111 are disposed about an antenna axis 115 within the array of slotted openings 113. The six slotted openings 111 are spaced apart from one another at angular intervals of
 radians (60°), and the six slotted openings 113 are spaced apart from one another at angular intervals of
 radians (60°). All twelve slotted openings 111 and 113 are coupled to a transmission line (not shown) located on the back side of the antenna 110. With twelve slotted openings, the antenna 110 has a higher directivity and a greater pattern roll-off from boresight to antenna horizon than, for example, the antenna 50, in FIG. 5, comprising four slotted openings.
 In a fifth embodiment, shown in FIG. 11, an antenna 120 comprises eight straight slotted openings 121 a, 121 b, . . . , and 121 h arrayed about an antenna axis 123. Each slotted opening 121 a-121 h is coupled to a transmission line 125 on the back side of the antenna 120, as shown in FIG. 12. A first end 127 of the transmission line 125 is connected to a first signal amplifier 131, and a second end 129 of the transmission line 125 is connected to a second signal amplifier 133. There is also provided a switching circuit (not shown) which enables either the first signal amplifier 131 or the second signal amplifier 133 to transmit a corresponding signal through the transmission line 125. A signal transmitted by the first signal amplifier 131 travels in a counter-clockwise direction, from the first end 127 to the second end 129. The input impedance of the second signal amplifier 133 provides an impedance load to the signal transmitted by the first signal amplifier 131. The counter-clockwise signal is coupled first into the straight slotted opening 121 a and last into the straight slotted opening 121 h. This coupling sequence produces an emitted signal having left-handed circular polarization.
 Similarly, a signal transmitted by the second signal amplifier 133 travels in a clockwise direction, from the second end 129 to the first end 127. The input impedance of the first signal amplifier 131 provides an impedance load to the signal transmitted by the second signal amplifier 133. The clockwise signal is coupled first into the straight slotted opening 121 h and last into the straight slotted opening 121 a. This coupling sequence produces an emitted signal having right-handed circular polarization. In this way, a single antenna can be used to transmit signals of either polarization. Alternatively, the second signal amplifier 133 can be replaced by a receiver (not shown), and the antenna 120 can be used to transmit left-handed circularly polarized signals via first signal amplifier 121 and to receive right-handed circularly polarized signals via the receiver. If the first signal amplifier is also replaced by a second receiver (not shown), both left-hand polarized and right-hand polarized signals can be received by the antenna 120.
 While the invention has been described with reference to particular embodiments, it will be understood that the present invention is by no means limited to the particular constructions and methods herein disclosed and/or shown in the drawings, but also comprises any modifications or equivalents within the scope of the claims.
|Citing Patent||Filing date||Publication date||Applicant||Title|
|US7250916||Jul 19, 2005||Jul 31, 2007||Novatel Inc.||Leaky wave antenna with radiating structure including fractal loops|
|US7265729 *||Jul 31, 2006||Sep 4, 2007||National Taiwan University||Microstrip antenna having embedded spiral inductor|
|US7423539||Aug 26, 2005||Sep 9, 2008||Impinj, Inc.||RFID tags combining signals received from multiple RF ports|
|US7525438||May 15, 2007||Apr 28, 2009||Impinj, Inc.||RFID tags combining signals received from multiple RF ports|
|US7528728||Aug 26, 2005||May 5, 2009||Impinj Inc.||Circuits for RFID tags with multiple non-independently driven RF ports|
|US7667589||Jul 14, 2004||Feb 23, 2010||Impinj, Inc.||RFID tag uncoupling one of its antenna ports and methods|
|US7868841||Apr 11, 2007||Jan 11, 2011||Vubiq Incorporated||Full-wave di-patch antenna|
|US7889151 *||Nov 8, 2007||Feb 15, 2011||The United States Of America As Represented By The Secretary Of The Navy||Passive wide-band low-elevation nulling antenna|
|US8797230||Jul 29, 2011||Aug 5, 2014||Harris Corporation||Antenna for circularly polarized radiation|
|US20050212674 *||Jul 14, 2004||Sep 29, 2005||Impinj, Inc., A Delaware Corporation||RFID tag uncoupling one of its antenna ports and methods|
|US20060049917 *||Aug 26, 2005||Mar 9, 2006||Impinj, Inc.||RFID tags combining signals received from multiple RF ports|
|US20060055620 *||Aug 26, 2005||Mar 16, 2006||Impinj, Inc.||Circuits for RFID tags with multiple non-independently driven RF ports|
|US20070018899 *||Jul 19, 2005||Jan 25, 2007||Waldemar Kunysz||Leaky wave antenna with radiating structure including fractal loops|
|EP1381112A2 *||Jun 13, 2003||Jan 14, 2004||Silvia Hofmann||Planar microwave antenna|
|EP1905126A1 *||Jul 10, 2006||Apr 2, 2008||NovAtel Inc.||Leaky wave antenna with radiating structure including fractal loops|
|WO2007009216A1||Jul 10, 2006||Jan 25, 2007||Earl Badger||Leaky wave antenna with radiating structure including fractal loops|
|WO2013158825A1 *||Apr 18, 2013||Oct 24, 2013||Xg Technology, Inc.||Mimo antenna design used in fading enviroments|
|U.S. Classification||343/770, 343/895, 343/769|
|International Classification||H01Q13/10, H01Q13/20, G03F7/09, H01P5/08, H01Q1/36, H01Q9/27, H01Q21/26|
|Cooperative Classification||H01Q13/106, H01Q1/36, H01Q13/20, G03F7/091, H01Q9/27, H01P1/2005|
|European Classification||H01P1/20C, H01Q13/10C, H01Q13/20, G03F7/09A, H01Q9/27, H01Q1/36|
|Aug 14, 2000||AS||Assignment|
|Mar 15, 2006||SULP||Surcharge for late payment|
|Mar 15, 2006||FPAY||Fee payment|
Year of fee payment: 4
|Mar 3, 2010||FPAY||Fee payment|
Year of fee payment: 8
|Mar 3, 2014||FPAY||Fee payment|
Year of fee payment: 12