|Publication number||US20040213342 A1|
|Application number||US 10/785,499|
|Publication date||Oct 28, 2004|
|Filing date||Feb 24, 2004|
|Priority date||Jun 30, 1998|
|Also published as||DE69939006D1, EP1038365A2, EP1038365B1, US6724844, WO2000001085A2, WO2000001085A3|
|Publication number||10785499, 785499, US 2004/0213342 A1, US 2004/213342 A1, US 20040213342 A1, US 20040213342A1, US 2004213342 A1, US 2004213342A1, US-A1-20040213342, US-A1-2004213342, US2004/0213342A1, US2004/213342A1, US20040213342 A1, US20040213342A1, US2004213342 A1, US2004213342A1|
|Original Assignee||Monisha Ghosh|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (8), Referenced by (10), Classifications (11)|
|External Links: USPTO, USPTO Assignment, Espacenet|
 This is a Divisional of application Ser. No. 09/107,546, filed Jun. 30, 1998.
 1. Field of the Invention
 The present invention is directed in general to digital signal processing, and in particular to receiver based methods and devices for improving decision feedback equalizer (“DFE”) performance in a trellis coded system.
 2. Background of the Invention
 In many digital communication scenarios (e.g. telephone transmission, broadcast TV transmission, cable etc.) The transmitted signal arrives at the receiver through more than one path in addition to the direct path. This condition is called “multipath” and leads to intersymbol interference (“ISI”) in the digital symbol stream. This ISI is compensated for in the receiver through an equalizer which in many cases is a DFE as shown in FIG. 1. U.S. Pat. No. 5,572,262 shows one method of combating these multipaths.
 A DFE 10 (FIG. 1) has two filter sections, a forward filter 12 and a feedback filter 16. The input to the forward filter 12 is the received data which includes the transmitted symbol sequence ak, noise nk and multipath hi. The input to the feedback filter 16 is the quantized equalizer output âk. The output of both the sections are summed 18 to form the final equalizer output ãk which is also the input to the next stage in a trellis-coded system, the trellis decoder. While a DFE performs better than a linear equalizer in severe ISI, the performance is limited by error propagation through the feedback filter 16 of the DFE 10. Error propagation occurs in the feedback filter 16 when the quantized equalizer output âk is not the same as the transmitted symbol ak. If an error is made in determining the symbol âk at the output of the slicer 11, this incorrect symbol is fed back to the input of the feedback filter 16 and propagates. In many systems which employ error correction codes like trellis codes and/or Reed-Solomon codes to obtain very low error rates at moderate SNRs, the “raw” symbol error rate (SER) at the equalizer output can be extremely high. For example, in the VSB system, at threshold in white noise the SER at the equalizer output is about 0.2. The increased error propagation due to these high SERs can cause the DFE to lose a couple of dB in performance as compared to the case of no error propagation. Additionally, the error propagation causes the error sequence at the equalizer output to be correlated, since it depends on past incorrect symbol decisions. This correlation has an adverse effect on the subsequent trellis decoder which is usually designed for a white noise sequence.
 Accordingly, it is an object of the invention to reduce the mean-squared-error (MSE) and correlation of the DFE output error sequence. This object is achieved by placing a short adaptive predictor filter after the DFE in order to whiten the error sequence. The ISI introduced into the data symbol stream by this filter is then compensated in the trellis decoder by the use of delayed decision feedback sequence estimation (DDFSE) as described in “Delayed decision-feedback sequence estimation,” by A. Duel-Hallen and C. Heegard, IEEE Trans. Commun., vol. COM-37, no. 5, pp. 428-436, May 1989.
 The invention has applications in any trellis coded system that utilizes a DFE for equalization, especially in cases where the SER after the equalizer is high and error propagation causes problems. An example is terrestrial transmission of digital TV signals.
 The invention can also be used in trellis coded systems with DFEs which are subject to colored noise interference. Again, the DFE cancels much of the interference but the adaptive predictor serves to whiten the noise further. This helps improve the trellis decoder performance.
 The invention accordingly comprises the several steps and the relation of one or more of such steps with respect to each of the others, and the apparatus embodying features of construction, combinations of elements and arrangement of parts which are adapted to effect such steps, all as exemplified in the following detailed disclosure, and the scope of the invention will be indicated in the claims.
 For a more complete understanding of the invention reference will be had to the following drawings:
FIG. 1 shows a standard DFE;
FIG. 2 shows a DFE in accordance with the invention; and
FIG. 3 shows a DFE in accordance with the invention during a training sequence.
FIG. 1 is a diagram of the standard decision feedback equalizer 10 (DFE). The DFE includes a forward filter 12, a slicer 14, a feedback filter 16 and a subtractor 18. Let ak be the transmitted trellis-coded symbol stream. The received signal rk
 after multi-path distortion and added noise nk can be written as where hi, i=0 . . . Lh−1 is the multipath channel of length lh and delay dh, and nk is the additive noise which in general is neither gaussian nor white. The forward filter 12 is used to remove the pre echo or ghosts in the received signal. The slicer 14 quantizes the signal ã to the nearest symbol âk. If an error is made in this quantization the error is passed to the feedback filter 16 and remains in the system. The output of the feedback filter 16 is subtracted from the output of the forward filter 12 to provide ãk. ãk is an estimate of the transmitted symbol ak plus, an error ek.
 It can also be expressed as:
 where fi, i=0 . . . Lf−1 are the forward equalizer taps, bi, i=1 . . . Lb are the feedback taps, df is the delay through the forward equalizer, db is the delay in the feedback equalizer and âk is the constellation point closet to ãk. In the absence of error propagation, i.e. if âk=ak, the error sequence ek at the equalizer output 20 is white. However, in most cases the error propagation causes this error sequence to be correlated, that is, the noise samples are no longer independent. The “colored” noise affects the performance of a trellis coder, because a trellis coder is optimized for performance in a channel having all white guassian noise.
 In accordance with the invention, as shown in FIG. 2, an adaptive filter 22 is placed at the output of the DFE 10 but before a trellis decoder (not shown). The output of filter 22 can be
 expressed as
 where (1, g1 , g 2, g3 . . . gLg) are the taps of the adaptive filter.
 Since ãk=ak+ek, then the adaptive filter output can be written
 If the filter taps are chosen so as to minimize the variance of e′k, the SNR of the sequence yk can be improved. In addition, since e′k is the prediction error sequence of the equalizer output error sequence ek, it will be white see Widrow and Stearns, “Adaptive Signal Processing,” (hereby incorporated by reference), at pages 99-116), which does not affect the performance of a trellis decoder.
 Training of the Adaptive Filter
 To minimize the error from the output of the DFE, or in other words to tune the adaptive filter taps g to the error ek, the adaptive filter 22 is first placed through a training sequence as shown in FIG. 3. In many applications, such as digital TV, the training sequence is part of the transmitted signal. After the equalizer 10 has converged (via blind means, without using the signal ak, or trained means which uses the signal ak) the adaptive filter 22 receives a training sequence which is the difference between the output of the DFE ãk and the transmitted symbol sequence ak. This difference is the error ek produced by the DFE.
ã−a k =e k (5)
 This error sequence ek is then input into the adaptive filter 22. The adaptive filter 22 forms an output sequence xk as shown in FIG. 3, where
g (k+1)= g (k)−μx k e (k)
 The filter taps gk are adapted using the LMS algorithm as follows where g= and e(k)=ek−1, ek−2, . . . ek−Lg]. This adaptation adapts the filter taps to minimize the mean squared, error ek 2, of the DFE.
 Since the trellis decoder uses the taps [g1, g2, . . . gLg] in a feedback loop, error propagation can also occur hence it is also beneficial to limit the size of the taps g during adaptation, so that the trellis decoder that uses these taps does not suffer error propagation. If g is too small, however, the efficiency of the adaptive filter is reduced. Accordingly, an additional power constraint is imposed on the LMS algorithm to limit the amplitude of the taps which reduces the error propagation in the DDFSE trellis decoder (described next). A parameter P is chosen such that it is required that
 At each step of the LMS algorithm this condition is tested, and if violated, the taps are rescaled appropriately.
 The Adaptive Filter and DDFSE
 Once the adaptive filter 22 is appropriately trained to minimize ek, ãk=ak+ek is input to the adaptive filter 22. The adaptive filter 22 although it has been trained to minimize ek, it will also distort ãk. Equation 9 shows this distortion and
 represents the output of adaptive filter 22 as follows: As stated above, if the filter taps g are chosen to minimize ek, the SNR of the sequence yk can be improved. yk, however, is a distorted ãk and includes the ISI introduced into the data stream by the adaptive filter 22. This distortion is then compensated for in the trellis decoder by use of delayed decision feedback sequence estimation (DDFSE)as described in A. Duel-Hallen and C. Heegard, “Delayed decision-feedback Sequence Estimation,” IEEE Trans. Common., Vol. Com-37, no. 5, pp. 428-436, May 1989, hereby incorporated by reference, and as summarized below.
 From the definition of yk, we see that an optimum trellis decoder which will remove the distortion of ãk, should minimize the
 metric (maximum likelihood decoding):
 This equation, however, requires past symbol sequences ak−i to be saved, and each tap gi in the adaptive filter therefore introduces more memory into the system which causes the number of steps of a trellis decoder to grow exponentially with the number of taps in the adaptive filter 22. Therefore an expanded trellis is necessary to accommodate the memory (ak−i) introduced by the adaptive filter 22.
 A suboptimum, but computationally less intensive way of performing the trellis decoding is to instead minimize the
 following metric:
 where the sequence âk−i,j, i=1, . . . Lg is the survivor symbol sequence associated with state j in the trellis. This scheme does not expand the number of states in the original trellis, but instead introduces decision-feedback in each of the trellis states. That is, since this scheme uses âk−i, which is merely an estimate of, rather than the actual value ak−i, there is no memory introduced into the system. Since there is no memory, an expanded trellis is not required, i.e. the number of states in the trellis remains the same even with the additional adaptive filter 22.
 There is the possibility of error propagation in this implementation and hence the precaution is taken in the LMS algorithm of limiting the amplitude of the filter taps. The optimum value of P will depend on the trellis code and application. In the United States HDTV example, simulation results indicate that a value of P=0.15 gives good performance.
 It will thus be seen that the objects set forth above, among those made apparent from the preceding description, are efficiently attained and, since certain changes may be made in carrying out the above method and in the construction set forth without departing from the spirit and scope of the invention, it is intended that all matter contained in the above description and shown in the accompanying drawings shall be interpreted as illustrative and not in a limiting sense.
|Cited Patent||Filing date||Publication date||Applicant||Title|
|US3723911 *||Sep 13, 1971||Mar 27, 1973||Codex Corp||Training adaptive linear filters|
|US5777910 *||Nov 19, 1996||Jul 7, 1998||Thomson Multimedia S.A.||Sparse equalization filter adaptive in two dimensions|
|US6118812 *||Jan 30, 1998||Sep 12, 2000||Lucent Technologies Inc.||Digital equalization in the presence of quantization noise|
|US6285709 *||Oct 31, 1997||Sep 4, 2001||3 Com Corporation||Error filtering in a hybrid equalizer system|
|US6570863 *||Nov 16, 1999||May 27, 2003||Electronics And Telecommunications Research Institute||Apparatus and method for adaptive CDMA detection based on constrained minimum mean squared error criterion|
|US6724844 *||Jun 30, 1998||Apr 20, 2004||Koninklijke Philips Electronics N.V.||Method and device for improving DFE performance in a trellis-coded system|
|US6934345 *||Jan 17, 2001||Aug 23, 2005||Adtran, Inc.||Apparatus, method and system for correlated noise reduction in a trellis coded environment|
|US20030193366 *||Apr 16, 2002||Oct 16, 2003||Tobe Barksdale||Demodulating|
|Citing Patent||Filing date||Publication date||Applicant||Title|
|US7194029 *||Oct 8, 2003||Mar 20, 2007||Broadcom Corporation||Multi-pair gigabit ethernet transceiver having adaptive disabling or circuit elements|
|US7483481 *||Aug 31, 2004||Jan 27, 2009||Adtran, Inc.||System and method for adaptively updating precoder taps|
|US7570701||Dec 4, 2007||Aug 4, 2009||Broadcom Corporation||Multi-pair gigabit ethernet transceiver|
|US7733952||Mar 20, 2007||Jun 8, 2010||Broadcom Corporation||Multi-pair gigabit Ethernet transceiver having adaptive disabling of circuit elements|
|US7801240||Nov 18, 2008||Sep 21, 2010||Broadcom Corporation||Multi-pair gigabit ethernet transceiver|
|US7801241||Aug 3, 2009||Sep 21, 2010||Broadcom Corporation||Multi-pair gigabit Ethernet transceiver|
|US8451885||Jun 8, 2010||May 28, 2013||Broadcom Corporation||Multi-pair gigabit ethernet transceiver having adaptive disabling of circuit elements|
|US8787439 *||Mar 13, 2012||Jul 22, 2014||Lsi Corporation||Decision feedforward equalization|
|US20120002762 *||Jan 5, 2012||Intelleflex Corporation||Single or dual complex subcarrier downconversion|
|US20130243066 *||Mar 13, 2012||Sep 19, 2013||Lsi Corporation||Decision feedforward equalization|
|International Classification||H04L25/03, H04B7/005, H04L1/00|
|Cooperative Classification||H04L2025/0349, H04L2025/03617, H04L2025/03382, H04L1/0054, H04L25/03057|
|European Classification||H04L1/00B5L, H04L25/03B1A7|