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Publication numberUS3146409 A
Publication typeGrant
Publication dateAug 25, 1964
Filing dateOct 27, 1960
Priority dateOct 27, 1960
Publication numberUS 3146409 A, US 3146409A, US-A-3146409, US3146409 A, US3146409A
InventorsLalmond Richard G
Original AssigneeSanders Associates Inc
Export CitationBiBTeX, EndNote, RefMan
External Links: USPTO, USPTO Assignment, Espacenet
Multiple coupler employing resonant effects to isolate the load circuits from each other
US 3146409 A
Abstract  available in
Previous page
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Claims  available in
Description  (OCR text may contain errors)

Aug. 25, 1964 R. G. LALMOND 3,146,409

MULTIPLE COUPLER EMPLOYING RESONANT EFFECTS TO ISOLATE THE LOAD CIRCUITS FROM EACH OTHER Filed Oct. 27, 1960 3 Sheets-Sheet l 46 m L |"*F I 44 M y 24 I 40 I 2 I 42 I 32 FIRST l so I SECOND OUTPUT I m *t m I OUTPUT 4a 34 as as I 22 2o Richard G. Lolmond INVEN TOR @/(QW ATTORNEY Aug. '25, 1964 R. G. LALMOND 3,146,409

MULTIPLE COUPLER EMPLQYING RESONANT EFFECTS TO ISOLATE THE LOAD CIRCUITS FROM EACH OTHER Filed Oct. 27 1960 5 Sheets-Sheet 2 A TTORNE Y 3,146,409 NG RESONANT EFFECTS TO ISOL ATE l Aug. 25, 1964 R. LALMOND MULTIPLE COUPLER EMPLOYI THE LOAD CIRCUITS FROM EACH OTHER 3 Sheets- Sheet 5 v Filed 001:. 2'7 1960 ATTENUATION FREQUENCY Richard G. Lolmond IN VE N TOR @/PW AT TORNE Y United States Patent 3,146,409 MULTIPLE C(IUIPLER EMPIJDYING RESONANT EFFECTS TI) ISUIATE THE LOAD CIRCUITS FRIIM EACH OTHER Richard (G. Lalmond, Nashua, NIL, assignor to Sander Associates, Inc, Nwhua, N.H., a corporation of Deiawwe Filed Oct. 27, 1360, Ser. No. 65,469 3 (Iiaims. (CI. 333--8) This invention relates to a multiple coupler. More particularly, it relates to a circuit using only passive elements to couple an alternating current source to a plurality of isolated loads. The coupler is particularly useful in connecting an antenna to a number of receivers which are isolated from each other, thereby preventing spurious signals generated in a receiver from reaching other receivers and degrading the signal-to-noise ratios therein.

A principal object of my invention is to provide an improved multiple coupler having the above characteristics, i.e., isolation of the various loads from each other While using only passive elements.

Another object of the invention is to provide a multiple coupler of the above type having a low insertion loss.

A further object is to provide a multiple coupler having the above characteristics over a broad band of frequencies.

Yet another object of the invention is to provide a multiple coupler of the above type which is reliable in operation, small in size and weight and yet relatively low in cost.

Other objects of the invention will in part be obvious and will in part appear hereinafter.

The invention accordingly comprises the features of construction, combination of elements and arrangement of parts which will be exemplified in the construction hereinafter set forth, and the scope of the invention will be indicated in the claims.

For a fuller understanding of the nature and objects of the invention, reference should be had to the following detailed description taken in connection with the accompanying drawings, in which:

FIGURE 1 is a schematic diagram of a coupler, embodying the principles of my invention, adapted to couple a source to two loads isolated from each other,

FIGURE 2 is a somewhat simplified version of the circuit of FIGURE 1, with the elements rearranged to illustrate one of the modes of operation,

FIGURE 3 is a simplified equivalent of the circuit of FIGURE 2,

FIGURE 4 is an equivalent of the circuit of FIG- URE 1,

FIGURE 5 is an equivalent of the circuit of FIGURE 4, arranged to illustrate the transformer mode of isolation,

FIGURE 6 is a response curve showing isolation between the two outputs of the coupler of FIGURE 1, and

FIGURE 7 is a diagram showing how the coupler of FIGURE 1 may be cascaded to increase the number of loads coupled to a single source.

In the following discussion, the various circuit parameters are identified by standard symbols with subscripts indicating the components associated with them. Thus R is the resistance of the component identified by the reference numeral 58.

Referring first to FIGURE 1, a multiple coupler embodying the principles of my invention includes an isolator 10 and generally also an input transformer 12. The coupler couples a source 14 connected to input terminals 16 and 18 to output loads indicated as resistors ice 20 and 22 across output terminals 24 and 26 and 28 and 30, respectively. The source 14 may, by way of example, be a receiving antenna and the resistors 20 and 22 the input impedances of receivers obtaining their input signals from the antenna.

The isolator 10 isolates the two outputs from each other, i.e., it substantially prevents interchange of energy between the terminals 24 and 26 on the one hand and the terminals 28 and 30 on the other. It includes an autotransformer 32, with identical windings 34 and 36 having an equal number of turns. A center tap 38 of the transformer 32 is connected to the transformer 12, and thus it serves as an input terminal for the isolator. A resistor 40 and a reactance unit 42 comprising an inductor 44 and capacitor 46 are connected in series across the transformer 32. The transformer 32 includes leakage inductances indicated by the inductors 48 and 50.

In considering the transfer of energy from the source 14 to the load resistors 20 and 22, the circuit of FIG- URE 1 may be redrawn as in FIGURE 2, with the input to the isolator 10, as seen from the tap 38, represented by a generator 56 in series with a resistor 58. Because of symmetry (L =L R =R the generator 56 impresses equal voltages across the idealized windings 34 and 36. However, because of the 1:1 ratio between these two windings, each of them induces in the other a voltage equal to the impressed voltage therein. The induced voltages are opposite in polarity from the impressed voltages, and therefore, there is no net voltage across either of the windings 34 or 36. Accordingly, the voltages across the two series arms comprising the inductor 48 and resistor 20, and the inductor 50 and resistor 22 are equal. It follows that equal power is delivered to the two load resistors. Furthermore, the voltages at the terminals 24 and 28 are equal. In other words, for power received from the source 14, the circuit of FIGURE 2 may be represented as in FIGURE 3, with the isolator 10 having essentially no effect on transmission of power to the resistors 20 and 22.

The manner in which isolation is obtained between the outputs of the isolator 10 will now be described in detail. The circuit of FIGURE 1 may be redrawn as in FIG- URE 4-, with a voltage 2 impressed across the terminals 24 and 26. Next, if the resistor 40 and reactance unit 42 are referred to the primary of the transformer 32 i.e., the winding 34 andinductor 48 when operating as in FIGURE 4, the circuit of FIGURE 5 results, with a resistor 40. and reactance unit 42' in series across the primary. Since the winding 34 in FIGURE 4 is the primary of an ideal transformer whose secondary includes the windings 34 and 36 in series, the turns ratio of this transformer is n l/2. The impedance transformation between the secondary and primary is equal to I1 i.e., 1/ 4. Therefore, the resistance and the reactance Therefore, onlythe impedance of the resistor 40 is reflected across the, primary.

Still referring to FIGURE 5, the voltages across the idealized windings 34 and 36 and the currents through them are equal. Accordingly, the current in the resistor 40' must be equal to the current in the resistor 58, and, therefore, the voltage drops across the resistors are equal.

However, the voltage across the resistor 40 is the same as the voltage across the winding 34, and subsequently the voltage across the resistor 53 equals the voltage across the winding 36. The voltage across the load resistor 22, resulting from the input voltage e is therefore zero.

It will be apparent that at low frequencies, where the effect of lead inductors associated with the resistor 40 is negligible, the reactance unit 42 may be eliminated, with a wide attenuation band width for operation in the above matter- However, at high frequencies use of the reactance unit is desirable, although of course there is a resulting limitation on attenuation band width. It will also be understood that if the source impedance represented by the resistor 58 has an reactive component, the resistor R should also be an element having a similar component of reactance.

In view of symmetry in the circuit of FIGURE 4, it will be apparent that the same result is obtained when a voltage is impressed between the terminals 28 and 30, and the resulting voltage at the terminals 24 and 26 is determined. Thus, there is complete isolation between the two outputs of the isolator 10.

Isolation achieved in the manner described above may be termed transformer isolation as opposed to parallel resonance isolation, also inherent in my multiple coupler. A detailed discussion of what is termed the parallel resonance isolation is difficult to accomplish as the precise theoretical explanation is not fully understood. It has been observed that the arrangement described above provides a unique capacity to provide isolation between the terminals 24 and 28 over a broad band of frequencies between a predetermined first and second frequency.

Thus, at the frequency f there is a parallel resonant circuit between the terminals 24 and 28, and the high impedance provided by the parallel resonance effectively isolates the loads connected to these terminals.

In FIGURE 6 I have plotted, as a function of frequency, the attenuation imposed by the isolator 10 (FIG- URE 1) on signals passing between the two outputs thereof. The frequency f corresponding -to transformer isolation, is characterized by a fairly broad peak, and the frequency f corresponding to parallel resonance isolation, is characterized by a sharp peak resulting from the relatively high Q nature of the reasonance. The'response curve was obtained from a unit designed to operate in the VHF region, and, in this particular unit, the 40 db attenuation bandwidth, i.e., f f was 40 percent of the center frequency f Greater attenuation in the center of the band may be obtained, at the expense of attenuation bandwidth, by moving the frequencies f and f closer together. With a given leakage inductance in the transformer 32 (FIG- URE 1), these frequencies may be varied by changing the values of the inductor and capacitor 46 in the reactance unit 42. It should be noted that, at both the frequencies f, and f the reactance unit 42 exhibits a net capacitive reactance. Therefore, a single capacitor may, in some cases be used instead of the inductor-capacitor combination. However, with only the capacitor, either the frequency f, or f may be controlled but not both, assuming a given leakage inductance. With the combination, both frequencies may be set at the values desired.

Returning to FIGURE 1, the transformer 12 is required for maximum transfer of power between the source 14 and the load resistors 20 and 22, unless the internal resistance of the source is equal to one half the resistance of the resistor 20 and 22, that is, unless there is an impedance match in the circuit of FIGURE 3. Ordinarily, the source and load resistances will be equal and, therefore, a 2:1 impedance match by the transformer 12 is required. This can easily be accomplished by a L-type transformer comprising a series inductor 72 and shunt capacitor 74.

In FIGURE 7 I have shown multiple couplers of the type described above may be cascaded to provide any desired number of outputs. Thus, the source 14 may be connected to the input of a coupler 76, including the isolator 10 and transformer 12, described above. The outputs of the isolator 10 are connected to input transformers 78 and 80 of multiple couplers 82 and 84, of the type described above, provided with isolators 86 and 88. Thus, the source 14 may be coupled to four loads connected to the outputs of the couplers 82 and 84, and the loads will be isolated from each other in the manner described above. Since the resistive elements in the multiple couplers do not absorb power from the source 14, the loss in each coupler is relatively low, approximately 0.1 db per stage. Therefore, a number of stages may be cascaded without appreciable degradation of signal-to-noise ratio.

Thus, I have described an improved multiple coupler adapted to couple a source between a pair of loads while isolating the loads from each other. The coupler is formed entirely of passive elements and, therefore, is characterized by high reliability together with low operating 7 costs. Isolation is provided, in the first place, by means of a novel autotransformer arrangement, and where isolation over a wide band of frequencies is desired, a parallel resonance mode may also be resorted to. The coupler is also relatively simple in construction and considerably less expensive to fabricate than prior units requiring active elements of various types.

It will thus be seen that the objects set forth above, among those made apparent from the preceding description, are efficiently attained and, since certain changes may be made in the above constructions without departing from the scope, of the invention, it is intended that all matter contained in the above description or shown in the accompanying drawings shall be interpreted as illustrative and not in a limiting sense.

It is also to be understood that the following claims are intended to cover all of the generic and specific features of the invention herein described, and all statements of the scope of the invention which, as a matter of language, might be said to fall therebetween.

What is claimed is:

1. A broad band multiple coupler comprising, in combination, an auto-transformer having first and second windings, the turns ratio of said windings being substantially unity, said transformer having a center tap and first and second end terminals on said first and second windings respectively which may be connected to respectively separate loads, a parallel branch connected between said first and second terminals, a source having an impedance connected between said center tap and a common reference point, said source providing energy over a broad range of frequencies between a predeterminedfirst and second frequency, said branch when referred across said first winding having an effective impedance, at said first frequency, substantially equal to the impedance of said source, said branch having a reactance component sulficient to form a parallel resonance circuit with the impedances of said windings between said first and second end terminals at said second frequency which parallel resonance provides a high impedance which effectively isolates the loads connected to these terminals, said first and second frequencies being spaced sufficiently to provide substantial isolation between said first and second terminals over a broad band of frequencies.

2. The combination defiened in claim 1 in which said branch includes a resistance and a reactance, the values of said resistance and reactances being selected to permit broad band operation of the coupler 3. A broad band multiple coupler comprising, in combination, an autotransformer having a center tap and two end terminals; a first source connected between said center tap and a common reference point, said source providing energy over a broad range of frequencies between a predetermined first and second frequency; a branch circuit connected between said end terminals, said branch circuit including a reactance in series with a resistance to resonate and thereby cancel lead inductances of said branch circuit at said first frequency; loads connected between said terminals and said reference point,

the total impedance of said branch at said first frequency being four times that of said source; the reactance of said branch being such at said second frequency as to resonate with twice the leakage reactance between said tap and said one of said terminals; and thereby provide parallel resonance which parallel resonance establishes a high impedance which effectively isolates said loads from each other.

References Cited in the file of this patent UNITED STATES PATENTS 2,115,059 Blumlein Apr. 26, 1938

Patent Citations
Cited PatentFiling datePublication dateApplicantTitle
US2115059 *Aug 7, 1936Apr 26, 1938Emi LtdHigh frequency electric transmission line
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US3428919 *Feb 9, 1966Feb 18, 1969NasaSignal multiplexer
US5045821 *Nov 9, 1990Sep 3, 1991Motorola, Inc.Broadband multi-phase hybrid
US5126702 *Dec 6, 1990Jun 30, 1992U.S. Philips CorporationCurrent supply means for wideband distribution
US5204644 *Jan 27, 1992Apr 20, 1993Rohde & Schwarz Gmbh & Co. KgCircuit arrangement for distributing or for combining radio-frequency power
US5347245 *Nov 5, 1993Sep 13, 1994Bark Lee YeeCATV signal splitter
US5412355 *Dec 3, 1993May 2, 1995Philips Electronics North America CorporationResonant balun with arbitrary impedance
US5469129 *Aug 29, 1994Nov 21, 1995Motorola, Inc.Impedance transforming three-port power divider/combiner using lumped elements
US6140889 *Mar 11, 1999Oct 31, 2000U.S. Philips CorporationHigh-frequency signal splitter
US9209774Sep 9, 2011Dec 8, 2015Technetix Group LimitedSignal splitter for use in MoCA/CATV networks
US20070127368 *Nov 21, 2006Jun 7, 2007Nippon Antena Kabushiki KaishaSignal Divider
EP0151784A2 *Dec 21, 1984Aug 21, 1985Richard Hirschmann GmbH & Co.High frequency distribution network
EP0151784A3 *Dec 21, 1984Dec 10, 1986Richard Hirschmann Radiotechnisches WerkHigh frequency distribution network
EP0652675A1 *Sep 16, 1994May 10, 1995Yee, Bark-LeeCATV signal splitter
EP1793494A1 *Nov 21, 2006Jun 6, 2007Nippon Antena Kabushiki KaishaSignal divider
WO2012035323A1 *Sep 9, 2011Mar 22, 2012Technetix Group LimitedSignal splitter for use in moca/catv networks
U.S. Classification333/131, 333/100, 333/119, 333/32
International ClassificationH03H7/00, H03H7/48
Cooperative ClassificationH03H7/482
European ClassificationH03H7/48C