|Publication number||US3668567 A|
|Publication date||Jun 6, 1972|
|Filing date||Jul 2, 1970|
|Priority date||Jul 2, 1970|
|Also published as||CA928809A, CA928809A1, DE2128688A1, DE2128688B2|
|Publication number||US 3668567 A, US 3668567A, US-A-3668567, US3668567 A, US3668567A|
|Inventors||Rosen Harold A|
|Original Assignee||Hughes Aircraft Co|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (2), Referenced by (45), Classifications (14)|
|External Links: USPTO, USPTO Assignment, Espacenet|
06-05-72 XR 396689567 v United States Patent 1 3,668,567
Rosen [4 1 June 6, 1972 54] DUAL MODE ROTARY MICROWAVE Primary Examiner-Hernian Karl Saalbach COUPLER Assistant Examiner--Marvin Nussbaum Attorney-James K. Haskell and Lawrence V. Link, Jr.  Inventor: Harold A. Rosen, Santa Monica, Calif.
 Assignee: Hughes Aircraft'Company, Culver City,
. Calif- 57 ABSTRACT  Filed: July 1970 Microwave coupling devices having input and output [2|] Appl No 51,869 rotatably mounted circular waveguide sections with a phase shifter and an orthogonal mode transducer coupled to the input circular waveguide section for converting a pair of I US. Cl. A, l, input signals to counterrotating circularly 333/98 TN, 343/756 polarized signals. A second orthogonal mode transducer, as-  Int. Cl ..H0lp 1/16, HOlp 5/ l2 Sociated with the output circular waveguide section, provides [5 8] Field Search "333/21, 21 l output signals of the proper phase for dual mode transmission 333 9, 98 TN; 343/756, 786 by a multiple feed horn antenna system.
 References Cited UNlTED STATES PATENTS 1 Claims, 13 Drawing Figures 2,713,151 7/1955 Farr ..333/21 x 3,394,375 7 7/1968 Vice et al ..343/756 x PATENTEUJUM s 1972 sum 1 or A iirii FRQRTR Anna/4 4 PATENTEDJUH 6 I972 SHEET 0F 4 mm Q Iil l gfilf 4 f j l i i I I i i QNmK mm DUAL MODE ROTARY MICROWAVE COUPLER BACKGROUND OF THE INVENTION This invention relates to dual mode microwave couplers and particularly to improved coupling devices of reduced complexity for applying output signals from a pair of rotating transmitter output terminals to an antenna feed network with isolation between signal channels and with the signals applied to the antenna input terminals being properly phased for transmission of a desired shaped beam pattern.
In certain applications such as communication satellites, it is necessary to apply energy from a pair of rotating transmitters or transmitter output multiplexers to input terminals of an antenna system. Economies and improved performance may be realized in the transmitter multiplexer units if sufiicient isolation between signal channels is provided; and reduction in size and weight of the antenna feed-coupler network may be obtained if the antenna input terminals are excited by signals of the proper phase for transmission of a desired shaped beam pattern.
SUMMARY OF THE INVENTION Therefore it is an object of the subject invention to provide an improved dual mode microwave coupler.
Another object is to provide an improved rotary coupler device of reduced complexity for coupling a pair of transmitter channels to a pair of input terminals of an antenna system such that isolation is provided between channels.
A further object is to provide a rotary joint of increased efficiency and reduced size, weight and complexity for directly feeding a pair of input terminals of a shaped beam antenna system.
The microwave coupling devices in accordance with the principles of the subject invention include input and output rotatably mounted circular waveguide sections. An orthogonal mode transducer and a phase shifter are coupled to the input circular waveguide section 'whereby linearly polarized input signals from a pair of transmitter multiplexer channels are converted to counterrotating circularly polarized signals. The output circular waveguide section includes a mode transducer for converting the counterrotating circularly polarized signals to a pair of linearly polarized signals suitable for directly feeding the input terminals of a shaped beam" antenna system.
BRIEF DESCRIPTION OF THE DRAWINGS The novel features of this invention, as well as the invention itself, will best be understood from the accompanying description taken in connection with the accompanying drawings, in which like characters refer to like pans, and in which:
FIG. 1 is a side elevational view, partially in phantom, of one embodiment of the dual mode rotary coupling device in accordance with the invention;
FIG. 2 is a sectional view taken along the line 2-2 of FIG. 1;
FIG. 3 is a sectional view taken along the line 3-3 of FIG. 1;
FIG. 4 is a schematic diagram of the coupling device of FIG.
FIG. 5 is a schematic and block diagram of a second embodiment of the dual mode rotary microwave coupling device in accordance with the principles of the invention;
FIG. 6 is a schematic and block diagram of a third embodiment of the rotary joint coupling device in accordance with the invention;
FIG. 7 is a front view of a portion of a communication satellite system incorporating the coupling device of the invention for explaining the operation thereof;
FIG. 8 is a plot of communication channels versus frequency for explaining the operation of the subject invention;
FIGS. 9a, 9b, 9c and 9d are diagrams of transmitted antenna power patterns for explaining the advantages of the couplers of the subject invention; and
FIG. 10 is a schematic and block diagram of a dual channel transmitter multiplexer system which could be utilized to drive the coupler devices in accordance with the subject invention.
DESCRIPTION OF THE PREFERRED EMBODIMENTS The coupler devices of the subject invention are indicated generally by the reference numeral 28 with one embodiment 28a being shown in FIGS. 1 through 4, and second and third embodiments 28b and 28c shown in FIGS. 5 and 6 respectively. Coupler 28 includes an input circular waveguide section 50 and an output circular waveguide section 52 coupled by a rotatable joint 65. 1
FIG. 7 shows a portion of a communication satellite 51 which could incorporate the coupler 28 and the subject invention may be better understood by first briefly considering the system thereshown. The satellite 51 has an antenna 20 with a parabolic reflector 22 illuminated by a pair of contiguous feed horns 24 and 26. As described in an application entitled Shaped Beam Antenna, filed July, 1970, by Harold A. Rosen and James S. Ajioka and assigned to the assignee hereof, and as will be summarized hereinafter, a beam shaped in one axis to provide a large coverage area with signals of approximately uniform power levels is desirable for many communication satellite applications. Such a beam pattern may be formed by excitingthe two feed horns with signals having a quadrature phase relationship.
The signals which excite horns 24 and 26 are applied from the rotary joint coupler 28 through waveguides 30 and 32. The input ports of the rotary joint 28 are excited by signals applied from combining arms (waveguides) 34 and 36 which are driven by transmitter multiplexer units 38 and 40 respectively. The transmitter multiplexer units are mounted on a support structure 42 together with other units such as receivers, signal processor units, power supplies, control units and positioning engines which are not relevant to the subject invention and are not shown.
FIG. 10 shows the transmitter multiplexer units 38 and 40 in greater detail. Each unit comprises six transmission channels having a bandwidth of 40 megahertz, for example, and including a circulator, an input filter, a power amplifier and an output filter. Each of the transmission channel paths are identified by a reference numeral corresponding to the channel number, with the odd numbered channels associated with combining arm 34 and the even numbered channels with combining arm 36.
The transmission multiplexer units are driven by ninety degree hybrid 44 energized by a frequency translation. unit 46 in response to a receiver unit 48. The frequency translation unit 46 operates to translate the received signal to the desired portion of the frequency spectrum for transmission.
One of the more important advantages of the subject invention is that due to the frequency separation between even and odd channels (see FIG. 8) the multiplexer units 38 and 40 may be simplified if proper isolation of the output signals from these units is maintained in rotary joint coupler unit 28. With the isolation provided by the coupler devices in accordance with the subject invention, the out of band attenuation requirements on the output filters of the multiplexers are reduced and economies may therefore be realized. For example the output filters, which could be the interdigital type, and the combining arms may be constructed of aluminum instead of INVAR in systems incorporating coupler 28.
The dual mode feature of the combination of antenna 20 and coupler 28 provides the desired broad uniform gain pattern with a reduction in size, weight, and complexityof the antenna feed-coupler network. As used herein, the dual mode feature refers to the provision of two independent antenna terminals each providing the same gain pattern and polarization sense but having differing senses of phase progression across the pattern. The importance of the two independent terminals in transmission is alleviating the above-described multiplexing problem encountered when multiple transmitters separated in frequency share the same antenna. It is noted that when only two transmitters are involved the provisions of two terminals eliminates the requirement of a transmitter output multiplexer entirely. When a large number of transmitters is required, the provision of two terminals permits connecting to each a set of transmitters having twice the adjacent channel frequencies separation thereby simplifying the design of the multiplexer.
The shaped beam feature provides a far field pattern which has a greater gain-bandwidth product than can be achieved with comparable conventional aperture excitation techniques Since in satellite communication applications the beam must cover a large prescribed area on earth to fulfill its objectives, the minimum gain achieved over the coverage area should be maximized rather than the beam center gain. As will be explained in detail subsequently, coupler 28 excites the input feed network of antenna with a pair of signals comprising approximately equal components of the signals from the multiplexer units 38 and 40 and the signals applied to the two feed horns are approximately in phase quadrature. The advantages of this type of excitation of horns 24 and 26 may be explained by reference to FIG. 9 which traces the development of the desired shaped beam transmission pattern. FIG. 9a shows the far field pattern for a parabolic reflector having a single on center feed. FIG. 9b shows a similar transmission pattern for a parabolic reflector having an off center feed and FIG. 90 depicts the pattern resulting from a reflector illuminated by a pair of feeds disposed on opposite sides of the center of the reflector. FIG. 9d shows the resultant improvement (more constant gain across a broader pattern) resulting from two off center feeds excited by a pair of signals in phase quadrature. This arrangement provides identical patterns for the output signals from each of the transmission multiplexer units.
Also it should be noted that in spinning satellite applications for the antenna 20 to maintain a fixed orientation the antenna section of the satellite must rotate with respect to the spinning platform 42, and hence the upper section of coupler 28 (FIGS. '7 and 8) must be rotatable with respect to the lower section.
The dual mode microwave rotary coupling device of FIGS. 1 through 4 exhibits the above-described advantages of minimum size, weight and complexity and fulfills the abovedescribed requirements of providing electrical isolation between the multiplexer output channels and properly phased signals to antenna 20. Referring now primarily to these lastmentioned figures, the rotary coupler unit 28a includes an input circular waveguide section 50 having rectangular input waveguide ports 54 and 56 spaced 90 degrees apart above the circumference of the circular waveguide section 50. Input ports 54 and 56 are adapted to be coupled to the output terminals of combining arms 34 and 36 (FIG. 7), and in association with septums 58 and 60 form an orthogonal mode transducer'5l, is. the linearly polarized signals applied from combining arms 34 and 36 launch linearly polarized signals within the circular waveguide section 50 which are spatially oriented 90 degrees relative to one another. Septums 58 and 60 are spaced the proper distance from the input ports 54 and 56 to cause the wave energy reflected from end section 51 back to the input ports to be in phase with the energy injected into the input ports. A plurality of irises 62 (one may be sufficient in some applications) vary the propagation velocity of the waves of one polarization relative to the other and hence perform the function of a polarization sensitive differential phase shifter. The design of the septums and irises for optimum performance is well documented in the literature such as the text, Principles and Applications of Waveguide Transmission, by George C. Southworth, published by D. Van Nostrand Company Inc., Princeton, New Jersey, 1956.
A rotatable joint 65 which may be of the noncontacting choke joint type, allows rotation between the input section 50 and the output section 52 of the coupler 28a. Output section 52 includes an orthogonal mode transducer 63 which comprises output ports 64 and 66 and septums 68 and 70, which elements operate in the same manner as described for orthogonal mode transducer Sll discussed above. Output ports 64 and 66 are adapted to be coupled to waveguides 30 and 32 (FIG. 7) which feed antenna 20.
In actuality the signals generated by each of the multiplexer units 38 and -30 contains a great many different frequency components grouped in channels separated by frequency zones equal to the bandwidth of a single channel (due to the even and odd multiplexing arrangement). However, for the purpose of clarity of explanation of the operation of the coupler 2% it will be assumed that each of the two output signals of the multiplexer units comprise a single frequency and that vectors depicting the transverse electric wave of the signals at any one point may be represented by the notation cos m and cos wgt. FIG. 4 analytically traces the signals as they progress through the coupler 28a. The signals applied from the transmitter multiplexer units 38 and 40 (FIG. 7) are applied to input ports 54 and 56 of circular waveguide section 50 and are spatially oriented degrees by means of the positioning of the input ports. The phase shifter which comprises the irises 62 develops counterrotating circularly polarized waves which may be TE circularly polarized waves, designated by the notation In the output section 52 of the coupler the signals maintain their circularly polarized form except for the addition of a phase angle 0 due to the rotation of the output section of the coupler relative to the input section. This rotation effect is accounted for by the designation of the signals as The orthogonal mode transducer 63 formed in the output circular section 52 by output ports 64 and 66 apply linearly polarized waves of orthogonal phase characteristics to each of the output ports as represented by the termcos (w t+0 sin (m r-19) and sin (ant-H9 cos (m r-0) which signals are applied to the feed horns 24 and 26 through coupling waveguide sections 30 and 32 respectively (FIG. 7).
A second preferred embodiment of the subject invention is shown in FIG. 5 and is indicated generally by reference numeral 28b. Coupler 28b is similar to the one (28a) shown in FIG. 1 except that the input signals from the transmission multiplexer units 38 and 40 are applied to input ports of a ninety degree hybrid junction 72 and the phase shift network 62 is eliminated. The output ports of the hybrid junction are coupled to the input ports of circular waveguide section 50. Again assuming that the signals applied from the transmission multiplexer units 38 and 40 are in the form cos w t and cos w t, the outputs signals from the hybrid junction 72 applied to input ports 54 and 56 are cos w t+ sin wzt) and mn w t+ cos m r).
w t). Because the signals applied to the input ports of the circular waveguide section 50 are in phase quadrature and are transformed into a space quadrature arrangement by orthogonal mode transducer 51, counterrotating circularly polarized waves are launched in the input section. The output section 52 of the coupler 28b is identical to that of coupler 28a discussed previously.
Referring now primarily to FIG. 6 which shows a third preferred embodiment of the subject invention, the output signals from the multiplexer units 38 and 40 are applied to input ports of a magic tee device 74. Magic tee 74 divides the input signals equally between a pair of output ports 76 and 78 and a differential phase shift is obtained by using a longer transmission path for one of the output signals. In FIG. 6 this increase in output paths is shown in block diagram form by a block 80, designated diff. path." It is understood that the path length difference between the signals applied from the different ports of magic tee 74 may be obtained at any point in the signal path to circular waveguide section 50. For example a portion of the differential path length may be included in the coupling between the magic tee 74 and the input ports of the circular waveguide section 50', and an additional portion obtained by staggering the input ports along the length of the circular waveguide section. Once again it will be noted that the signals applied to the input ports of circular waveguide section 50 are in phase quadrature (due to the differential path length) and are in a space quadrature relationship due to the effect of the orthogonal mode transducer input section 51. The output section 52 of the coupler unit 28c is identical to that described previously relative to coupler 28a.
The configuration of FIGS. 5 and 6 afford the designer a means of reducing the overall length of the circular waveguide sections in those applications where space along the central axis of the coupler is critical. The simplicity of the design of the couplers in accordance with the principles of the subject invention eliminates tolerance buildups encountered in more complex arrangement thereby relaxing tolerances on components of the remaining units and reducing beam pattern perturbations associated with imperfections in the coupling-antenna feed network.
Thus, there has been described an improved and reliable microwave coupling device for applying a pair of output signals from a transmitter multiplexer system through a rotatable joint to a pair of input terminals of an antenna system such that the signals are isolated during transmission through the coupler thereby simplifying the design of the multiplexer system. The signals are converted in form at the output section of the coupler such that they are properly phased for efficient transmission of a relatively wide beam pattern.
Although one specific satellite application has been disclosed herein to illustrate the advantages and features of the subject invention it will be understood that the couplers in accordance with the subject invention are applicable to a wide range of applications. For example, instead of coupling the output ports of the circular waveguide section 52 directly to feed horns 24 and 26 they may be coupled to any one of a number of well known antenna input terminal networks. For instance the antenna terminal network could process the signals applied thereto for application to a four-feed hom arrangement; for example, having a pair of centrally disposed offset feed horns radiating a sum" signal and outer feed horns in conjunction with the inner pair radiating a difference signal. Additionally, although the ports for coupling microwave energy to and from the various units have been shown herein as the waveguide type such as ports 54 and 56, it will be understood that other well known techniques such as probes or slotted wall coupling means may be used in place thereof. Also, the disclosure deals mainly with a transmission application but it will be appreciated that the invention may be readily used with a receiving system or with a combination of the transmit and receive functions. For example, with feed horns that allow two orthogonal linear modes, the received signals (of one polarization) could be coupled through the rotary joint 28 by means of a coaxial cable, having rotary couplings, routed through the center of the sections and 52.
What is claimed is: l. A microwave coupling device comprising: first and second rotatably mounted circular waveguide sections; first means responsive to first and second linearly polarized input signals for launching counterrotating circularly polarized signals in said first waveguide section, said first means including a pair of input ports formed in said first circular waveguide section with approximately a ninety degree interval about the circumference of the section therebetween, a pair of septums in said first circular waveguide section approximately orthogonally disposed to each other, and a differential phase shifter comprising at least one iris disposed within said first circular waveguide section; and
second means including first and second output ports formed in said second circular waveguide section, for providing first and second linearly polarized output signals at said first and second output ports respectively, such that each said output signal has first and second linearly polarized signal components with the first signal component of each said output signal being derived from said first input signal and being substantially in phase quadrature with the other said first signal component, and the second signal component of each output signal being derived from said second input signal and being substantially in phase quadrature with the other said second signal component.
2. The device of claim 1 wherein the vectors representative of the transverse electric field of said linearly polarized input signals are designated cos (0,! and cos (0 wherein m, and 0 are the radian frequencies of said first and second input signal respectively; said first means includes means for converting said input signals into signals of the form and said second means includes means for providing said first linearly polarized output signal in the form cos cu t sin m and said second linearly polarized output signal in the form sin w cos (0 3. The device of claim 1 wherein the output ports of said second means are separated by approximately a degree interval about the circumference of said second circular waveguide section.
4. A microwave coupling device comprising:
first and second rotatably mounted circular waveguide sections;
first means responsive to first and second linearly polarized input signals for launching counterrotating circularly polarized signals in said first waveguide section, said first means including an orthogonal mode transducer having a pair of input ports formed in said first circular waveguide section; and a ninety degree hybrid junction having a pair of input ports adapted to be energized by said linearly polarized input signals, and having a pair of output ports coupled to said pair of input ports of said orthogonal mode transducer; and
second means including first and second output ports formed in said second circular waveguide sections, for providing first and second linearly polarized output signals at said first and second output ports respectively, such that each said output signal has first and second linearly polarized signal components with the first signal component of each said output signal being derived from said first input signal and being substantially in phase quadrature with the other said first signal component, and the second signal component of each output signal being derived from said second input signal and being substantially in phase quadrature with the other said second signal component.
5. The device of claim 4 wherein the input ports of the orthogonal mode transducer are separated by approximately a ninety degree interval about the circumference of said first circular waveguide section.
6. The device of claim 5 further including a different pair of approximately orthogonally disposed septum plates in each said first and second circular waveguide sections.
7. The device of claim 4 wherein the output ports of said second means are separated by approximately a ninety degree interval about the circumference of said circular waveguide section.
8. A microwave coupling device comprising:
first and second rotatably mounted circular waveguide sections;
first means responsive to first and second linearly polarized second means including first and second output ports formed in said second circular waveguide section, for providing first and second linearly polarized output signals at said first and second output ports respectively, such that each said output signal has first and second linearly polarized signal components with the first signal component of each said output signal being derived from said first input signal and being substantially in phase quadrature with the other said first signal component, and the second signal component of each output signal being derived from said second input signal-and being substantially in phase quadrature with the other said second signal component.
9. The device of claim 8 wherein the output ports of said second means are separated by approximately a degree interval about the circumference of said second circular waveguide section.
10. The device of claim 9 further including a different pair of approximately orthogonally disposed septum plates in each said first and second circular waveguide sections.
|Cited Patent||Filing date||Publication date||Applicant||Title|
|US2713151 *||Mar 29, 1946||Jul 12, 1955||Farr Harold K||Two channel rotary joint|
|US3394375 *||Nov 4, 1966||Jul 23, 1968||Northern Electric Co||Automatic tracking system for linearly polarized electromagnetic waves|
|Citing Patent||Filing date||Publication date||Applicant||Title|
|US3731235 *||Nov 3, 1971||May 1, 1973||Gte Sylvania Inc||Dual polarized diplexer|
|US3731236 *||Aug 17, 1972||May 1, 1973||Gte Sylvania Inc||Independently adjustable dual polarized diplexer|
|US3838362 *||Jun 29, 1973||Sep 24, 1974||Emerson Electric Co||Diplexing coupler for microwave system|
|US3906407 *||Jan 11, 1974||Sep 16, 1975||Cgr Mev||Rotary wave-guide structure including polarization converters|
|US3924205 *||Sep 3, 1974||Dec 2, 1975||Andrew Corp||Cross-polarized parabolic antenna|
|US3963990 *||Feb 27, 1974||Jun 15, 1976||Communications Satellite Corporation (Comsat)||Interference reduction circuit|
|US4117423 *||Sep 23, 1976||Sep 26, 1978||Hughes Aircraft Company||Dual mode multiphase power divider|
|US4119967 *||May 21, 1976||Oct 10, 1978||Teledyne, Inc.||Microwave dual mode non-interfering CW and pulsed signal system method and apparatus|
|US4141013 *||Sep 24, 1976||Feb 20, 1979||Hughes Aircraft Company||Integrated circularly polarized horn antenna|
|US4492938 *||Sep 21, 1982||Jan 8, 1985||Harris Corporation||Symmetrically-configured variable ratio power combiner using septum polarizer and quarterwave plate|
|US4613836 *||Nov 12, 1985||Sep 23, 1986||Westinghouse Electric Corp.||Device for switching between linear and circular polarization using rotation in an axis across a square waveguide|
|US4704611 *||Jun 11, 1985||Nov 3, 1987||British Telecommunications Public Limited Company||Electronic tracking system for microwave antennas|
|US4757281 *||Apr 22, 1987||Jul 12, 1988||Alcatel Espace||Rotary microwave joint device|
|US4989011 *||Oct 23, 1987||Jan 29, 1991||Hughes Aircraft Company||Dual mode phased array antenna system|
|US5032804 *||May 22, 1989||Jul 16, 1991||Motorola, Inc.||Frequency agile transmitter antenna combiner|
|US5162808 *||Dec 18, 1990||Nov 10, 1992||Prodelin Corporation||Antenna feed with selectable relative polarization|
|US5349364 *||Jun 26, 1992||Sep 20, 1994||Acvo Corporation||Electromagnetic power distribution system comprising distinct type couplers|
|US5376905 *||Aug 23, 1993||Dec 27, 1994||Hughes Aircraft Company||Rotary vane variable power divider|
|US5760660 *||Oct 8, 1996||Jun 2, 1998||Matsushita Electric Industrial Co., Ltd.||Orthogonal polarized wave branching filter and its manufacturing method|
|US5877660 *||Jul 24, 1997||Mar 2, 1999||Nihon Dengyo Kosaku Co., Ltd.||Phase shifting device with rotatable cylindrical case having driver means on the end walls|
|US6025809 *||Jul 31, 1998||Feb 15, 2000||Hughes Electronics Corporation||Antenna radiating element|
|US6154181 *||Dec 14, 1998||Nov 28, 2000||Thomson Licensing S.A.||Electromagnetic wave transmitter/receiver|
|US6181221 *||Oct 6, 1998||Jan 30, 2001||Hughes Electronics Corporation||Reflective waveguide variable power divider/combiner|
|US6225875||Oct 6, 1998||May 1, 2001||Hughes Electronics Corporation||Dual sidewall coupled orthomode transducer having septum offset from the transducer axis|
|US6664866 *||Dec 8, 2000||Dec 16, 2003||Mitsubishi Denki Kabushiki Kaisha||Generator of circularly polarized wave|
|US6727776||Feb 7, 2002||Apr 27, 2004||Sarnoff Corporation||Device for propagating radio frequency signals in planar circuits|
|US8736396 *||Jul 23, 2010||May 27, 2014||Sony Corporation||Radio communicating device, rotational structure, and electronic device|
|US9287903 *||Oct 5, 2011||Mar 15, 2016||Sony Corporation||Signal transmission apparatus, electronic instrument and signal transmission method|
|US9401536||Nov 12, 2014||Jul 26, 2016||Ayecka Communication Systems||Dual band antenna configuration|
|US20110026443 *||Jul 23, 2010||Feb 3, 2011||Sony Corporation||Radio communicating device, rotational structure, and electronic device|
|US20120093041 *||Oct 5, 2011||Apr 19, 2012||Sony Corporation||Signal transmission apparatus, electronic instrument and signal transmission method|
|CN102457309A *||Oct 11, 2011||May 16, 2012||索尼公司||Signal transmission apparatus, electronic instrument and signal transmission method|
|CN102457309B *||Oct 11, 2011||Dec 14, 2016||索尼半导体解决方案公司||信号传送设备、电子仪器和信号传送方法|
|EP0022401A1 *||Jun 27, 1980||Jan 14, 1981||Thomson-Csf||Broad-band polariser with low ellipticity-ratio and microwave equipment with the same|
|EP0243888A1 *||Apr 23, 1987||Nov 4, 1987||Alcatel Espace||Microwave device having a rotating joint|
|EP0357085A1 *||Sep 1, 1989||Mar 7, 1990||CSELT Centro Studi e Laboratori Telecomunicazioni S.p.A.||A coaxial-waveguide phase shifter|
|EP0369857A1 *||Nov 8, 1989||May 23, 1990||Thomson Tubes Electroniques||Microwave load in a short oversized waveguide|
|EP0490054A1 *||Oct 15, 1991||Jun 17, 1992||Roke Manor Research Limited||Improvements in or relating to rotatable joints for communication lines|
|EP0641036A1 *||Aug 18, 1994||Mar 1, 1995||Hughes Aircraft Company||Rotary vane variable power divider|
|EP0834953A1 *||Oct 7, 1996||Apr 8, 1998||Matsushita Electric Industrial Co., Ltd.||Orthogonal polarized wave branching filter and its manufacturing method|
|EP0993064A1 *||Oct 1, 1999||Apr 12, 2000||Hughes Electronics Corporation||Dual sidewall coupled orthomode transducer|
|EP1487049A1 *||Jun 9, 2004||Dec 15, 2004||Marconi Selenia Communications S.P.A.||A polarisation alignment system using waveguide differential phase shifters, and an antenna unit including such a system|
|EP1492191A1 *||Mar 25, 2003||Dec 29, 2004||Mitsubishi Denki Kabushiki Kaisha||Rotary joint|
|EP1492191A4 *||Mar 25, 2003||Jun 1, 2005||Mitsubishi Electric Corp||Rotary joint|
|WO2016075695A1||Nov 11, 2015||May 19, 2016||Ayecka Communication Systems||Dual band antenna configuration|
|U.S. Classification||333/21.00A, 333/117, 343/756|
|International Classification||H01P1/16, H01P1/161, H01P1/06, H04J1/08, H04J1/00|
|Cooperative Classification||H01P1/067, H04J1/08, H01P1/161|
|European Classification||H01P1/161, H01P1/06C2B, H04J1/08|