|Publication number||US4559489 A|
|Application number||US 06/537,696|
|Publication date||Dec 17, 1985|
|Filing date||Sep 30, 1983|
|Priority date||Sep 30, 1983|
|Publication number||06537696, 537696, US 4559489 A, US 4559489A, US-A-4559489, US4559489 A, US4559489A|
|Inventors||David C. Vacanti, John C. Read, Jimmy S. Takeuchi|
|Original Assignee||The Boeing Company|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (25), Referenced by (18), Classifications (10), Legal Events (4)|
|External Links: USPTO, USPTO Assignment, Espacenet|
This invention relates to the field of power dividers and, more specifically, to the use of such dividers with radio frequency (RF) power sources.
Power control systems which deliver input RF power to several output ports are typically very lossy. Many of such systems use transformers and transmission lines coupled to absorptive attenuators. Unfortunately, these systems do not deliver a large amount of their input power to their output ports, so such systems are not power efficient. Furthermore, many of these systems deliver power to output ports which have been turned off, which wastes power and makes it unavailable for other output ports.
For example, U.S. Pat. Nos. 4,028,632, 3,986,147 and 3,928,804 to Carter et al describe systems having an N-port circulator and isomismatch devices. The impedance mismatches, however, are fixed impedance transmission line mismatches and are not remote-controllable.
One of the objects of this invention is a highly efficient power controller which delivers virtually all of the input RF power to its output ports.
It is also an object of this invention to have a power efficient power controller which can be connected to a variable number of output ports.
Another object of this invention is a power controller which delivers power to several output ports and which can be easily adjusted to deliver no power to output ports that are turned off.
Yet another object of this invention is an efficient power controller which allows easy adjustment of the amount of power switched to any of its output ports.
Additional objects and advantages of this invention are set forth in the description which follows and in part would be obvious from that description or may be learned by practice of the invention. The objects and advantages of this invention may be realized by the apparatus pointed out in the appended claims.
The power controller of this invention uses variable reactive elements in its power distribution circuitry to deliver virtually all of the input power to the output ports. By using variable reactive elements, the amount of power delivered to any output port can be easily adjusted. If an output port is turned off, the power distribution circuitry can be adjusted to deliver virtually no power to that port.
The total power from the input (less insertion loss) source is always available to those ports which are still active. Virtually none of the power is absorbed at the off ports and the total power available may be apportioned as desired to the active ports.
To achieve the objects and in accordance with the purpose of this invention, as embodied and as described below, the power controller of this invention comprises a source of input power; a plurality of power output ports; and a first number of power distribution means coupled to the input power source and the power output ports for delivering substantially all of the input power to the plurality of output ports, each of the power distribution means receiving a fraction of input power, selectively transmitting a portion of that fraction of the input power to the output ports coupled to that power distribution means, and reflecting out the portion of the fraction of input power not transmitted to its coupled output ports.
More specifically, a power controller according to this invention for selectively distributing power supplied by a power source to n (where n is greater than one) output ports comprises n-1 circulators connected in series between the power source and an nth output port; and n-1 variable reflection coefficient devices each associated with and connected to a different one of the circulators and to a different one of the output ports, each of the variable reflection coefficient devices receiving input power from its associated circulator, transmitting a selective portion of the received input power to its associated output port, and reflecting back to its associated circulator the portion of the received input power not transmitted to its associated output port.
The accompanying drawings, which are incorporated in and which form a part of the specification, illustrate embodiments of the invention and, together with the description, explain the principles of the invention.
FIG. 1 shows an embodiment of a power controller of this invention for supplying input power to two output ports;
FIGS. 2 and 2a show variable reflection coefficient devices which can be used with the power controller shown in FIG. 1;
FIG. 3 shows a branch line coupler which can be used with the varable reflection coefficient device shown in FIG. 2; and
FIG. 4 shows an embodiment of a power controller of this invention for supplying input power to several output ports.
FIG. 1 shows a power controller 1 according to this invention which supplies input power from an RF input port 10 to output ports 21 and 22. In accordance with the present invention, the power controller includes a first number of power distribution means coupled to a source of input power and to power output ports for delivering substantially all of the input power to the output ports. Each of the power distribution means receives a fraction of input power, selectively transmits a variable portion of that fraction of input power to the power output ports coupled to that power distribution means, and reflects out the portion of the received fraction of input power not transmitted to its coupled output ports. In power controller 1 shown in FIG. 1, circulator 30 and variable reflection coefficient device 40 receive input power from RF input port 10, transmit a portion of that power to output port 22, and reflect out to the output port 21 via a power distribution line 23 the portion of the input power not transmitted to output port 22.
Circulator 30 is a conventional three terminal circulator. It sends the RF power from RF input port 10 into input/output terminal 41 of variable reflection coefficient device 40. It also sends to output port 21 via the power distribution line 23 any reflected power received from device 40 via input/output terminal 41.
The present invention also includes means for setting a reflection coefficient between zero and one to indicate the portion of power to be transmitted to the associated output port. Variable reflection coefficient device 40 has a set terminal 43 which is used to adjust the transmission coefficient r, or alternatively the reflection coefficient 1-r, of device 40 to a value between zero and one. The transmission coefficient r indicates what portion of the power received from input port 10 will be transmitted to output port 22, while the reflection coefficient 1-r indicates what portion of the RF input power is reflected back through circulator 40. For example, when r=0.1, only one tenth of the input power is transmitted to output port 22 and nine-tenths of that power is reflected.
Since the portion of the input power which is not transmitted to the output port is reflected back out to circulator 32 and to output port 21, virtually all of the input power from RF input port 10 is divided between output ports 21 and 22. By adjusting set terminal 43, the portions of the input power outputted to ports 21 and 22 can be adjusted. If output port 22 is turned off, for example, then r of device 40 can be set to zero so virtually all of the input power will be delivered to output port 21.
An embodiment of the variable reflection coefficient device 40 is shown in greater detail in FIG. 2. Device 40 includes a branch line coupler circuit 45, an example of which is shown in FIG. 3. Branch line coupler circuit 45 in FIG. 3 is a microstrip circuit which includes two horizontal legs 142 and 144 and two vertical legs 141 and 143 connected to form a square. The width of the horizontal legs and of the vertical legs are different. For example, for the 3 db coupler required for circuit 45, the series impedance should be 35.35 ohms and the shunt impedance should be 50 ohms. So in this case is also assumed to be 50 ohms. For a microstrip circuit in a circuit board whose dielectric constant is 2.2 and thickness is 0.010 inches, a 50 ohm line is 0.031 inches wide and a 35 ohm line is 0.053 inches wide. The length of these lines is 1/4 of the center operating frequency wavelength.
Alternatively, branch line coupler circuit 45 could include a waveguide or a coaxial circuit.
In FIGS. 2 and 3, input/output terminal 41 is shown in the upper left hand corner of device 40 and the output terminal 42 is shown at the lower left hand corner of device 40. Without any external circuitry, branch line coupler circuit 45 would divide the input power received at terminal 41 such that half of the power would appear at the upper right hand corner of circuit 45 and half the power would appear at that circuit's lower right hand corner. By adding reactive components to the upper and lower right hand corners of circuit 45, the amount of input power transmitted to output terminal 42 and reflected out of input/output terminal 41 can be adjusted.
In FIG. 2, the lower and upper right hand corners are denoted as 48a and 48b, respectively. In accordance with the present invention the power controller of this invention includes a variable reactive means coupled to the branch line coupler circuit. In FIG. 2, a transmission line 50 of length l1 and varactor diode 52 are coupled to terminal 48a. Similarly, transmission line 60 of length l2 and varactor diode 62 are coupled to terminal 48b. The length of transmission lines l1 and l2 can have the same or different lengths depending upon the application.
Varactor diodes 52 and 62 provide a variable capacitance at RF frequencies. Each varactor diode and transmission line combination provide a specific reactance for the variable reflection coefficient device 40. The value of the reactance provided at terminals 48a and 48b determines the value of r for device 40.
The value of the reflection coefficient seen at terminals 48a & b is proportional to impedance mismatch between the hybrid transmission line impedance and the impedance of the reactance element at the operating frequency. For example if the impedance at 48a is 50 Ω(Z MIN) and the impedance at the end of l1 was 70 Ω(Z MAX) the reflection coefficient can be calculated by: ##EQU1## For this example 1-r=0.167.
The lengths of transmission lines l1 and l2 have the property of altering the actual impedance seen at the output ports 48a & b due to the varactor diode. These transmission line lengths and their characteristic impedance alter the limited impedance range of the varactor diode and transform this into the desired values to achieve high and low levels of reflection coefficients.
The operation of elements 50-54 will be described with the understanding that elements 60-64 behave analogously. A voltage variable capacitance device, such as the varactor diode 52 has a capacitance that is determined by the voltage across that diode. To set that voltage, RF choke 53 and a variable power supply 54 are connected to the junction of varactor diode and transmission line 50.
Typically, RF choke 53 is a transmission line which is one or two times narrower than transmission line 50. RF choke 53 isolates the RF signals from power supply 54 because it appears as a very high impedance to RF frequency signals. To the constant voltage signals from power supply 54, however, choke 53 appears as a very low impedance, hence the bias voltage from supply 54 can pass through choke 53 to a set the capacitance of varactor diode 52.
To provide an even higher impedance for the input RF power, the length of RF choke 53 is set to about 1/4 of the wave length of the RF power and the RF choke is connected to the power supply by large printed circuit board capacitors (65, 66) to ground which act as low impedance at RF frequencies.
The capacitance of DC blocking capacitors 67 and 68 is chosen to be large at the RF operating frequencies so that they contribute an insignificant reactance or impedance in the circuit. Alternatively, DC blocking capacitors 65 and 66 may be removed if RF chokes 53 and 63 are moved directly to the left of varactor diodes 62 and 52 and connected across those diodes as in FIG. 2a.
The voltage of power supply 54 is set via terminal 43a just as the voltage of power supply 64 is set by terminal 43b. Preferably, terminals 43a and 43b are electronically controlled for speed and convenience. Terminals 43a and 43b together form set terminal 43 in FIG. 2.
For example, if the varactor diodes 52 and 62 are set to 1 picofarad, reactance of a 1 picofarad capacitor at 100 Megahertz operating frequency is computed by: ##EQU2##
The reflection Coefficient due to this reactance is computed if for example the impedance at 48a is 50 ohms. ##EQU3##
FIG. 4 shows an embodiment of the present invention to divide input power for N output ports. A circulator and a variable reflection coefficient device correspond to all but output port N. Specifically, output port 1 corresponds to circulator 200 and variable reflection coefficient device 203, output port 2 corresponds to circulator 210 and variable reflection coefficient device 213, output port 3 corresponds to circulator 220 and variable reflection coefficient device 223, and output port N-1 corresponds to circulator 290 and variable reflection coefficient device 293. Output port N does not correspond to a circulator and variable reflection coefficient device, but N is coupled to circulator 290 and receives that portion of the input power which is not sent to any of the other output ports.
Circulators 200, 210, 220 and 290 function similarly to circulator 30 in that power input to a circulator is sent to the associated variable reflection coefficient device. That variable reflection coefficient device reflects certain of that power back to the circulator which then transmits that power via power distribution lines 204, 214, 224 and 294 to the next circulator or, in the case of circulator 290, to output port N.
The input voltage from RF input 10 is sent via circulator 200 to variable reflection coefficient device 203 having a transmission coefficient, r1. The voltage output to port 1 equals r1 times the input voltage and the voltage reflected back through circulator 200 and into circulator 210 equals (1-r1) times the input voltage. Circulator 210 delivers that reflected power into device 213 which has a transmission coefficient of r2. Thus, output port 2 receives r2 of its incident input voltage or r2 x (1-r1) times the input voltage to the controller.
If r1 and r2 equaled 1/2, output port 1 would receive 1/2 of the RF input voltage and output port 2 would receive 1/4 that input voltage. The amount of voltage reflected into circulator 220 is also equal to 1/4 the input voltage.
The other variable reflection coefficient devices similarly split the power input to them between their output ports and the following circulator according to their reflection coefficients. The power reflected by variable reflection coefficient device 293 is output to port N.
|Cited Patent||Filing date||Publication date||Applicant||Title|
|US3305797 *||Apr 24, 1964||Feb 21, 1967||Emerson Electric Co||Microwave switching networks|
|US3400342 *||Sep 1, 1964||Sep 3, 1968||Sanders Associates Inc||Voltage controlled microwave phase shifter|
|US3422378 *||Oct 19, 1965||Jan 14, 1969||Hazeltine Research Inc||Compensating means for minimizing undesirable variations in the amplitude of a reflected wave|
|US3422438 *||Nov 30, 1965||Jan 14, 1969||Marston Arthur E||Conjugate pair feed system for antenna array|
|US3423699 *||Apr 10, 1967||Jan 21, 1969||Microwave Ass||Digital electric wave phase shifters|
|US3477028 *||Dec 28, 1966||Nov 4, 1969||Bell Telephone Labor Inc||Balanced signal mixers and power dividing circuits|
|US3479615 *||Oct 20, 1966||Nov 18, 1969||Us Army||Varactor continuous phase modulator having a resistance in parallel with the varactor|
|US3506930 *||Jul 18, 1967||Apr 14, 1970||Collins Radio Co||Broadband multilevel phase modulation system employing digitally controlled signal reflection means|
|US3555447 *||Dec 18, 1968||Jan 12, 1971||Bell Telephone Labor Inc||Signal reflector and circulator networks for synchronizing and combining the outputs of a plurality of oscillators|
|US3571762 *||Oct 6, 1969||Mar 23, 1971||Us Air Force||High frequency digital diode phase shifter|
|US3571765 *||Sep 15, 1969||Mar 23, 1971||Bell Telephone Labor Inc||Quantized phase shifter utilizing open-circuited or short-circuited 3db quadrature couplers|
|US3646467 *||Nov 2, 1970||Feb 29, 1972||Raytheon Co||Solid-state electromagnetic energy amplifier system|
|US3676803 *||May 1, 1970||Jul 11, 1972||Communications Satellite Corp||Electronically tunable matching circuit for circulators|
|US3768045 *||Oct 5, 1971||Oct 23, 1973||Korea Inst Sci & Tech||Wide range variable phase shifter|
|US3769610 *||Jun 15, 1972||Oct 30, 1973||Philco Ford Corp||Voltage controlled variable power divider|
|US3909751 *||Dec 28, 1973||Sep 30, 1975||Hughes Aircraft Co||Microwave switch and shifter including a bistate capacitor|
|US3928806 *||Nov 8, 1974||Dec 23, 1975||Us Army||Power dividing and combining techniques for microwave amplifiers|
|US3986147 *||Oct 3, 1975||Oct 12, 1976||The United States Of America As Represented By The Secretary Of The Army||Power divider and power combiner utilizing isolator-mismatch and isolator-reflector devices|
|US4004255 *||Jul 2, 1975||Jan 18, 1977||Compagnie Industrielle Des Telecommunications Cit-Alcatel||Microwave frequency phase modulator|
|US4028632 *||Sep 17, 1975||Jun 7, 1977||The United States Of America As Represented By The Secretary Of The Army||Power dividing and combining techniques for microwave amplifiers|
|US4205282 *||Aug 21, 1978||May 27, 1980||Westinghouse Electric Corp.||Phase shifting circuit element|
|US4288763 *||Sep 18, 1979||Sep 8, 1981||General Microwave Corporation||Analog phase shifter|
|US4301432 *||Aug 11, 1980||Nov 17, 1981||Motorola, Inc.||Complex RF weighter|
|JPS5583314A *||Title not available|
|SU708441A1 *||Title not available|
|Citing Patent||Filing date||Publication date||Applicant||Title|
|US4661993 *||Oct 12, 1984||Apr 28, 1987||At&T Company||Technique for improving radio system performance during fading|
|US4823096 *||Jan 11, 1988||Apr 18, 1989||Harris Corporation||Variable ratio power divider/combiner|
|US4933680 *||Sep 29, 1988||Jun 12, 1990||Hughes Aircraft Company||Microstrip antenna system with multiple frequency elements|
|US5039995 *||Nov 23, 1988||Aug 13, 1991||Gec Plessey Telecommunications Limited||Distributed antenna system|
|US5109204 *||Dec 3, 1990||Apr 28, 1992||Honeywell Inc.||High power RF precision attenuator|
|US5233317 *||Oct 3, 1991||Aug 3, 1993||Honeywell Inc.||Discrete step microwave attenuator|
|US5270824 *||Dec 30, 1991||Dec 14, 1993||Zenith Electronics Corporation||AGC circuit for double conversion digital television tuner|
|US6066992 *||Aug 12, 1998||May 23, 2000||Hughes Electronics Corporation||Variable ISO attenuator using absorptive/reflective elements and latching|
|US6816031 *||Dec 4, 2001||Nov 9, 2004||Formfactor, Inc.||Adjustable delay transmission line|
|US6992546 *||Dec 22, 2004||Jan 31, 2006||Ipr Licensing, Inc.||Electronic phase shifter with enhanced phase shift performance|
|US7015773 *||Jan 31, 2001||Mar 21, 2006||Ipr Licensing, Inc.||Electronic phase shifter with enhanced phase shift performance|
|US7057474 *||Nov 9, 2004||Jun 6, 2006||Formfactor, Inc.||Adjustable delay transmission lines|
|US7239220||Jun 6, 2006||Jul 3, 2007||Formfactor, Inc.||Adjustable delay transmission line|
|US7683738||Jul 3, 2007||Mar 23, 2010||Formfactor, Inc.||Adjustable delay transmission line|
|US20050099246 *||Nov 9, 2004||May 12, 2005||Formfactor, Inc.||Adjustable delay transmission lines|
|US20050104687 *||Dec 22, 2004||May 19, 2005||Ipr Licensing, Inc.||Electronic phase shifter with enhanced phase shift performance|
|US20060208830 *||Jun 6, 2006||Sep 21, 2006||Formfactor, Inc.||Adjustable Delay Transmission Line|
|EP0361417A2 *||Sep 27, 1989||Apr 4, 1990||Hughes Aircraft Company||Microstrip antenna system with multiple frequency elements|
|U.S. Classification||333/1.1, 333/116, 333/128, 333/81.00A|
|International Classification||H01P5/12, H01P5/04|
|Cooperative Classification||H01P5/12, H01P5/04|
|European Classification||H01P5/04, H01P5/12|
|Sep 30, 1983||AS||Assignment|
Owner name: BOEING COMPANY THE SEATTLE, WA A CORP.OF DE
Free format text: ASSIGNMENT OF ASSIGNORS INTEREST.;ASSIGNORS:VACANTI, DAVID C.;READ, JOHN C.;TAKEUCHI, JIMMY S.;REEL/FRAME:004180/0859
Effective date: 19830929
|Apr 3, 1989||FPAY||Fee payment|
Year of fee payment: 4
|Jun 1, 1993||FPAY||Fee payment|
Year of fee payment: 8
|Jun 16, 1997||FPAY||Fee payment|
Year of fee payment: 12