|Publication number||US4664116 A|
|Application number||US 06/601,525|
|Publication date||May 12, 1987|
|Filing date||Apr 18, 1984|
|Priority date||Apr 18, 1984|
|Publication number||06601525, 601525, US 4664116 A, US 4664116A, US-A-4664116, US4664116 A, US4664116A|
|Inventors||Mousa N. Shaya, Barry L. Wyshogrod|
|Original Assignee||Hewlett-Packard Company|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (7), Non-Patent Citations (2), Referenced by (44), Classifications (8), Legal Events (8)|
|External Links: USPTO, USPTO Assignment, Espacenet|
In monitoring the heart action of a patient having a pacemaker, it is essential to positively identify the pacemaker pulses contained in the signals detected via body electrodes if the software programs used for analysis are to function properly. Falsely identifying other signal components as pace pulses is as undesirable as failing to identify the true pace pulses. Although the pace pulses generally have an amplitude that is greater than steady high frequency noise, identification on the basis of amplitude alone is not feasible because the amplitudes of motion and muscle artifacts and QRS waves are often as great or greater than the amplitude of the pace pulses. Identification of pace pulses on the basis of amplitude is further complicated by the fact that the baseline often drifts at a low frequency and the fact that the absolute amplitudes of the signals vary widely. Identification of a pace pulse on the basis of width holds little promise because the widths of the pulses supplied by different makes of pacemakers vary from tens of microseconds to 2.5 milliseconds. Identification of the pace pulses must be sensitive to both positive-going and negative-going pace pulses. For these reasons, prior art apparatus has not identified the pace pulses in a satisfactory manner.
In accordance with this invention, the signals detected via the body electrodes are passed through a high pass filter to one input of a comparator. The filter suppresses baseline wander, the ECG waves and the artifacts due to movement and muscle action, so that only pace pulses, noise spikes and high frequency noise reach the comparator. The output of the filter is also applied to means for deriving a threshold wave that is applied to the other input of the comparator. The means for deriving the threshold wave operates to suppress the effects of pace pulses on its amplitude and to cause it to have a minimum amplitude when steady high frequency noise is absent and an amplitude equal to the sum of the minimum amplitude and a value that varies with the amplitude of the peaks of steady high frequency noise when such noise is present. Under these conditions, the amplitude of the pace pulses will exceed that of the threshold wave so as to cause the comparator to change state and thus indicate that a pace pulse is present. Because the threshold wave has an amplitude that is at least as great as the peaks of steady high frequency noise, this noise does not cause false identifications.
Derivation of the threshold wave may be accomplished by a number of circuits, but in the embodiment shown, the circuit includes means for rectifying the signals passed by the high pass filter, means for deriving an average value thereof which has a time constant such that the average value is relatively unaffected by pace pulses and noise spikes, means for providing sufficient gain for the average value to be greater than the peaks of steady high frequency noise, and means for adding a fixed increment to the average value so as to provide the minimum value.
If it is desired to indicate the presence of a pace pulse regardless of polarity, the output of the high pass filter is applied to one input of each of two comparators, and opposite polarities of the threshold wave are respectively applied to the other input so that one comparator will change state in response to a positive pace pulse and the other comparator will change state in response to a negative pace pulse.
FIG. 1 is a schematic diagram illustrating a preferred embodiment of this invention;
FIG. 1A illustrates the type of signals supplied to a pace pulse identifier from electrodes attached to a patient;
FIG. 1B illustrates the signals at the output of the high pass filter employed and the relationship of the positive and negative threshold thereto; and
FIG. 1C illustrates the portions of the signal at the output of the rectifier that lie on the positive side of the AC axis.
In the embodiment of FIG. 1, an EKG machine 2 provides signals detected via the body electrodes. As illustrated in FIG. 1A, the signals vary about a drifting baseline B and include a muscle and motion artifact M, three QRS complexes QRS1, QRS2 and QRS3 that are derived from different heart contractions, positive pace pulses P2 and P3 that respectively initiate the immediately following contractions represented by QRS2 and QRS3, noise spikes N1 and N2 and steady high frequency noise HF that may be caused by other electrical equipment. Pace pulses detected via the body electrodes may be of either polarity, so P4 and P5 are included in addition to P2 and P3 for completeness and explanatory purposes.
The signals of FIG. 1A provided by the EKG machine 2 are coupled to the input of a high pass filter 4 having a low frequency cut-off that is above the highest frequency of significance contained by the QRS complexes, the muscle and motion artifact M and the baseline drift so that the output of the high pass filter 4 is free from these components as illustrated by FIG. 1B. The output of the high pass filter 4 is applied to the negative input of a comparator C1 and via a resistor 6 to the positive input of a comparator C2. The output of the high pass filter 4 is also applied to means 8 for deriving the threshold wave previously referred to.
In this particular embodiment, the means 8 is comprised of a rectifying operational amplifier A1 having its non-inverting input connected to the output of the filter 4, its output coupled to ground via a diode d, a resistor 10 and a resistor 12 that are connected in series in the order named, and its inverting input connected to the junction of the resistors 10 and 12. For reasons to be set forth below, the values of the resistors 10 and 12 are such as to provide a gain of a little more than 3.14 so that the signal at the output of the amplifier A1 appears as indicated in FIG. 1C.
The output of the amplifier A1 is connected via a resistor 14 to the inverting input of an operational amplifier A2 having its non-inverting input connected to ground and its output connected to its inverting input via a parallel combination of a resistor 16 and a capacitor 18 so that the amplifier A2 operates as an inverting integrator of unity gain. A minimum value for the threshold wave is provided as follows. Resistors 20 and 22 are connected in series between a point of positive DC voltage and ground, and a resistor 24 having the same value as the resistors 14 and 16 is connected between the junction of the resistors 20, 22 and the inverting input of the amplifier A2.
Although the output of the amplifier A2 is derived from the positive signals of FIG. 1C, it is, because of the inversion of A2, a negative threshold wave having an amplitude relationship to the signals at the output of the filter 4 as indicated by the dashed wave -T of FIG. 1B. The time constant provided by the resistor 16 and the capacitor 18 is such that the contribution of the pace pulses P2 and P4 and of the noise spikes N1 and N2 to the output of the integrating amplifier A2 is suppressed, thus making the output have a minimum value equal to the DC voltage derived from the voltage divider 20, 22 when steady high frequency noise HF is absent. When, however, high frequency noise is present, as in the right half of FIG. 1B, the output of the itegrating amplifier A2 becomes more negative by a voltage value that varies with the amplitude of the high frequency noise HF. Preferably, it is at least equal to and even slightly greater than the envelope of the positive half-cycles of the high frequency noise HF. Because of the time constant involved, the threshold wave does not reach its maximum value until several cycles of HF have occurred. This means that the comparator will change state so as to falsely identify a cycle such as F of FIG. 1B as a pace pulse; but this occurs only when the electrical equipment causing the high frequency noise HF is turned on or its state of operation is changed. Such infrequent false identification can be taken into account by the algorithm used to process the signals.
In this particular embodiment of the invention, the increase in negative voltage in response to HF is derived in the following way. It is reasonable to assume that the steady state high frequency noise at the output of the high pass filter 4 is sinusoidal. If the rectifying amplifier A1 had unity gain, the average value of the half-sinusoids derived by the integrating amplifier A2 would equal the amplitude of HF divided by π. Therefore, if a gain of π is provided by the rectifying amplifier A1, the average value derived by the integrating amplifier A2 will be equal to the peak amplitude of the high frequency noise HF. Although not necessary, it is preferable that the gain of the rectifying amplifier A1 be slightly greater than π, e.g., 3.6, in order to provide an extra margin of noise rejection, as may be required if HF is not sinusoidal. The output of the integrating amplifier A2, at which -T appears, is connected to the negative input of C2.
A positive threshold wave which is ilustrated by a dashed line +T in FIG. 1B is derived from the negative threshold wave by inverting it in any suitable manner as with an operational amplifier A3. The negative threshold wave is applied via a resistor 26 to the inverting input of the amplifier A3. A resistor 28 which is equal in value to the resistor 26 is connected between the output of A3 and its inverting input, and the non-inverting input of A3 is connected to ground. The positive threshold wave +T produced at the output of A3 is applied to the non-inverting input of the comparator C1 via a resistor 30, and a resistor 32 is connected between the noninverting input of C1 and its output. A resistor 34 is connected between the non-inverting input of C2 and its output, and the outputs of C1 and C2 are connected via a resistor 36 to a point of positive potential. Resistors 6, 30, 32 and 34 provide hysterysis.
The time constant of the integrating amplifier A2 determined by the resistor 16 and the capacitor 18 can have different values, but a value equal to at least ten times the width of wide pace pulses has been found to work well. If the time constant is too short, pace pulses and noise spikes will increase the values of the threshold waves so as to decrease the sensitivity. Sensitivity is also decreased as the minimum value of the threshold wave is increased. Obviously, if the time constant is so short that the pace pulses appear with full ampltude in the threshold waves, the states of the comparators C1 and C2 would not change and the circuit would be inoperative.
Whereas it is preferable for the variable increment of voltage that is added to the minimum value of the threshold wave to at least equal the amplitude of the steady high frequency noise, a somewhat lesser amplitude could be used if the minimum value were increased, but this reduces the sensitivity.
The negative threshold wave -T can be derived in numerous ways other than that shown, e.g., the output of the filter 4 could be applied to a peak detector and a DC voltage could be added to it. It is also apparent that a full wave rectifier could be used in place of the half-wave rectifier associated with the amplifier A1, in which event its gain could be halved. In fact, the gain can be introduced at any point between the output of the high pass filter 4 and the inputs of the comparators C1 and C2 to which the threshold waves are applied.
The following values of impedance components and the following active devices have been found to give excellent results:
______________________________________R6 1K R24 464K A1R10 11K R26 10K A2 LF412 typeR12 4.22K R28 10K A3 op. amp.R14 464K R30 1K C1R16 464K R32 1 MEG LM393 typeC18 0.1 uf R34 1 MEG C2 comparatorR20 10K R36 10KR22 237 ohm R38 100K______________________________________
The overall operation of the pace pulse detecting apparatus is as follows. Assume that the signal from the EKG machine 2 contains pace pulses such as P2 and P3 of FIG. 1A as well as QRS complexes such as QRS1, QRS2 and QRS3. The high pass filter 4 eliminates the slow baseline drift, the muscle and movement artifacts M and the QRS complexes as indicated in FIG. 1B, but the pace pulses, noise spikes and high frequency noise HF remain. As seen in FIG. 1B, the positive threshold wave +T is above the positive peaks of the high frequency noise HF. This is because of the amplification in the amplifier A1 that is equal to or greater than π and because of the fixed DC level provided by the voltage divider 20, 22. Thus, even when the signals have zero value or little or no high frequency noise, as at the left side of FIG. 1B, the positive threshold wave +T will have a given value, and the negative threshold wave -T will have a like negative value.
When no pace pulses are present, the outputs of the comparators C1 and C2 are in a high state. If a positive pace pulse such as P2 or P3 appears, the output of C1 drops to a low state for the duration of the pace pulse; and if a negative pace pulse such as P4 or P5 appears, the output of C2 drops to a low state for the duration of the pace pulse. The pulses produced by these changes in state are sufficient for identification purposes, but because we desire the output of the circuit to be well defined, the outputs of C1 and C2 are connected to the anode of a diode d1, its cathode is connected to ground via a resistor 38 and the cathode of d1 is connected to the input of a one-shot multivibrator 40 that is triggered by negative edges. When the outputs of C1 and C2 are high, d1 conducts and the input of the multivibrator 40 is high, but the presence of a pace pulse causes the output of one of C1 and C2 to go low, so as to turn off d1 and cause the input of the one-shot multivibrator 40 to drop to ground and fire the multivibrator 40. A high amplitude pulse of noise such as N2 will cause the output of the comparator C1 to drop to a low state, unfortunately firing the one-shot multivibrator 40, but such noise spikes do not occur often, and these false indications can be handled by the algorithms.
If it were not for the minimum value of the threshold waves provided by the voltage divider 20,22, any amount of noise, no matter how small, would cause one of the comparators C1 and C2 to change to a low state and thus falsely identify the noise as a pace pulse.
If the pace pulse identification circuit is to identify pace pulses of one polarity, only one threshold wave of that polarity and one of the comparators C1 and C2 are required.
In the embodiment of the invention shown in FIG. 1, the negative threshold wave -T was derived first and the positive threshold wave +T was derived by inverting -T, but the positive threshold wave +T could be derived first and the negative threshold wave could be derived by inversion.
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|U.S. Classification||607/27, 600/510|
|International Classification||A61B5/0402, A61B5/0472, A61N1/37|
|Cooperative Classification||A61B5/7207, A61B5/0472|
|Feb 2, 1987||AS||Assignment|
Owner name: HEWLETT-PACKARD COMPANY, PALO ALTO, CA, A CORP. OF
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