|Publication number||US5063446 A|
|Application number||US 07/392,500|
|Publication date||Nov 5, 1991|
|Filing date||Aug 11, 1989|
|Priority date||Aug 11, 1989|
|Also published as||CA2021093A1, DE4024806A1|
|Publication number||07392500, 392500, US 5063446 A, US 5063446A, US-A-5063446, US5063446 A, US5063446A|
|Inventors||James J. Gibson|
|Original Assignee||General Electric Company|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (6), Non-Patent Citations (4), Referenced by (114), Classifications (12), Legal Events (5)|
|External Links: USPTO, USPTO Assignment, Espacenet|
This invention relates to an apparatus for transmitting auxiliary information in a television signal.
This invention will be described in terms of combining an auxiliary (e.g., digital) audio signal with a standard television signal for transmission purposes, however it should be appreciated that the invention is not intended to be limited to this application.
P. R. J. Court, in U.S. Pat. No. 3,231,818 describes a subscription television system wherein the normal audio carrier is encoded with subscription information and program sound is provided on a frequency modulated carrier placed in the vestigial sideband of the television signal. In this instance the frequency modulated carrier is located at 1.0 MHz below the picture carrier.
R. B. Dome, in U.S. Pat. No. 2,635,140 describes a television signal format wherein blue picture signal is modulated on a carrier located in the vestigial sideband of a green picture signal. Dome recognized that the energy of TV signals is concentrated in spectral bands located at integral multiples of the horizontal line frequency. He further recognized that, to effectively separate the signals, it would be advantageous to condition the blue signal to fall between the spectral bands occupied by the green picture signal. Since the blue picture signal is a TV signal, its energy is also concentrated in spectral bands at integral multiples of the line frequency. Locating the blue picture signal between the spectral bands of the green picture signal is accomplished by locating the green picture signal carrier at an odd multiple of one-half the line frequency.
It follows that to effectively separate an auxiliary signal (e.g., a sound signal), combined with a TV signal, the energy of the auxiliary signal should be concentrated between the spectral bands of the TV signal.
However, the energy spectrum of analog sound signals is relatively flat over the frequency band which is typically 20 Hz to 20 kHz. If the sound signal is converted to digital format, e.g., binary, duo binary, etc., the spectral band representing the signal is appreciably broadened (e.g., 350 kHz). It does not occur concentrated in spectral bands located at multiples of the line frequency.
It is an object of the present invention to provide a method and apparatus for conditioning the energy of an auxiliary signal to be concentrated in spectral bands without loss of signal information content.
The present invention apportions auxiliary signal into two intermediate signals including, in part, mutually exclusive portions of said auxiliary signal and polarity inverts portions of the signal. Further apparatus quadrature phase modulates a carrier having a frequency which is a multiple of the line frequency of a video signal. The quadrature phase modulated signal is thereafter combined with a TV signal for transmission.
In a further embodiment of the invention apparatus for detecting the auxiliary signal, transmitted in a TV signal, includes detecting the received signal to generate baseband auxiliary signal. The baseband auxiliary signal is multiplied with two signals having a 90 degree phase relationship and a frequency which is a multiple of the line frequency. Portions of the products of the multiplication are delayed an integral number of line intervals and delayed and nondelayed products are combined to form recovered decoded auxiliary signal.
FIG. 1 is a spectral diagram showing the spectrum of a video channel including an auxiliary carrier in the vestigial sideband.
FIG. 2 is a block diagram of a video signal encoder including apparatus for adding an auxiliary digital sound signal to the vestigial sideband of the TV signal.
FIG. 3 is a block diagram of circuitry for concentrating the auxiliary signal in predetermined spectral bands.
FIG. 4 is a timing diagram useful in describing the operation of the circuitry of FIGS. 3 and 7.
FIGS. 5 and 8 are block diagrams of alternate circuitry for concentrating the auxiliary signal in predetermined spectral bands.
FIG. 6 is a block diagram of a receiver including circuitry for processing an auxiliary signal transmitted in the vestigial sideband of a TV signal.
FIGS. 7 and 9 are block diagrams of alternate specific apparatus for recovering the auxiliary signal.
FIG. 1 shows the signal spectrum of a broadcast television signal which for NTSC is limited to a 6 MHz band. The television signal, ignoring the auxiliary carrier and its sidebands, includes luminance, chrominance and synchronizing components which are modulated on a video carrier. The modulated carrier is vestigial sideband filtered to remove signal frequencies in the lower sideband from approximately 0.75 MHz below the video carrier. A sound carrier is added to the video signal and resides at the upper extremity of the video channel. The television signal components located in the vestigial sideband spectra consist primarily of lower frequency luminance components which are concentrated in spectral bands centered on integral multiples of the horizontal line frequency.
The signal to be added, in accordance with this invention, is an auxiliary carrier shown (by way of example) centered at approximately 0.75 MHz below the video carrier. The sidebands of the auxiliary carrier are conditioned to occur between the spectral bands occupied by the luminance component. In the diagram the bandwidth of the auxiliary signal is shown to extend approximately 500 kHz on either side of the auxiliary carrier providing at least a 500 kHz information bandwidth. The auxiliary signal in this example is separated from the video carrier by 250 kHz to preclude interference therewith. This spacing or guardband prevents the auxiliary signal from producing undesirable interference in the audio signals of receivers having intercarrier sound detection systems.
Refer to FIG. 2 which illustrates a generalized environment in which the invention may be implemented. In the exemplary system the invention is incorporated to encode an auxiliary sound signal for transmission with a TV signal. It is to be understood, however, that the invention may be utilized to encode any signal not having its energy concentrated at integral multiples of the horizontal line frequency for transmission in a TV signal.
In FIG. 2 the elements 10-26 form a standard TV signal encoder for generating and transmitting a standard TV signal. Video signal from a source 10, which may be a television camera is applied to a video processor 12. Video processor 12 generates a baseband composite video signal, including synchronizing components, and applies the composite signal to an RF modulator 14, which responsive to the composite signal amplitude modulates a radio frequency video carrier. The modulated video carrier is applied to a vestigial sideband filter which limits the frequency components of the modulated signal to conform to the spectrum shown in FIG. 1.
Audio signals from an audio source 18 are applied to a sound processor 20. Processor 20 may include compansion circuitry or other conventional circuitry to precondition the audio signal prior to transmission. The preconditioned audio signal from the sound processor 20 is applied to an RF modulator 22, wherein it frequency modulates a carrier having a frequency 4.5 MHz (NTSC) above the picture carrier frequency. The modulated composite signal from the vestigial filter and the modulated sound signal from the modulator 22 are applied to a signal combiner 24 which, absent an auxiliary signal, forms a standard TV broadcast signal.
The audio signal from the audio source 18 is also applied to a digitizer and processor 28 wherein the audio signal (or signals in the case of stereo signals) is digitized and formatted in serial form. The signal provided by the processor 28 may be in a binary bit stream format, in duo binary format, etc. The formatted signal is coupled to a spectral conditioner 30, which concentrates the energy of the applied signal in spectral bands centered on odd multiples of one-half the line frequency. The signal from the spectral conditioner 30 is applied to a modulator 32 which, responsive to the video carrier, produces a single sideband modulated carrier. The output of the modulator 32 is a carrier having a frequency approximately 0.75 MHz below the video carrier and modulated with the auxiliary signal. The signal from modulator 32 is applied to the combiner 24 wherein it is additively combined with the modulated composite video signal.
FIG. 3 illustrates a first embodiment of the spectral conditioner 30 shown in FIG. 2. The circuitry of FIG. 3 (and FIG. 4) requires three operating signals; 1) a square wave signal (FH /2) of half-line frequency, 2) a cosinusoidal signal of frequency ω=2πkfH, where k is an integer and fH corresponds to the frequency of the signal FH, and 3) a sinusoidal signal of frequency ω=2πkfH. These three signals are generated in a conventional phase-locked-loop (PLL) circuit 31 (FIG. 2) responsive to a horizontal synchronizing signal FH provided by the video processor 12.
In FIG. 3, input signal is coupled to multiplexing circuitry 301, which, responsive to the signal FH /2 alternately couples the input signal to connections 01 and 02 for periods of one horizontal line interval. The signal applied to connection 01 is coupled to the input connection of a one horizontal line interval delay element 302 and to the minuend input connection of a subtracter 304. The output connection of the delay element 302 is coupled to the subtrahend input connection of the subtracter 304. For one horizontal line interval prior to input signal being coupled to connection 01, no signal is coupled to connection 01. Therefore, at the beginning of each line interval that signal is applied to connection 01, the delay element 302 contains no data. Consequently during the line interval that signal is coupled to connection 01, delay element 302 applies no signal to the subtracter 304, and the signal applied to connection 01 passes through the subtracter 304 unaltered. During this line interval the data for this line interval is loaded into the delay element 302 and appears at the output of delay element 302 during the subsequent line interval. However, during the subsequent line interval the input signal is disconnected from connection 01 so that only signal provided by delay element 302 is coupled to subtracter 304. This signal is output by the subtracter with its polarity inverted. The output of substracter 304 is designated S1 and illustrated in FIG. 4. Alternate horizontal line periods of signal are similarly processed by delay element 303 and subtracter 305. The output signal provided by the subtracter 305 is designated S2 in FIG. 4.
In FIG. 4 the waveform labeled FH represents the horizontal synchronizing signal and the row of blocks labeled input represents the auxiliary signal. Each of the blocks A, B, C, etc., represents a horizontal line interval of signal information. The signals S1 and S2 represented by the rows of blocks designated S1 and S2 contain signal information from alternate lines of the input signal. It can be seen that there is 100 percent redundancy in the combined signals S1 and S2. Note that the elements in both signal paths pass fullband signals. Signal is coupled through one path or the other at all times so there is no loss of information. Also note that the combination of delay element and subtracter is arranged in the form of a subtractive 1-H comb filter, which as is well known passes signal energy in spectral bands centered at odd multiples of one-half the line frequency.
The signal S1 from subtracter 304 is coupled to a multiplier 306 wherein it is multiplied by a carrier signal of constant frequency kfH. The signal S2 from subtracter 305 is coupled to a multiplier 307 wherein it is multiplied by a carrier signal of constant frequency kfH but 90 degrees out of phase with respect to the carrier signal applied to multiplier 306. Output signals from multipliers 306 and 307 are summed in an adder 308 to form a quadrature modulated output signal which is applied to the modulator 32 (FIG. 2).
FIG. 5 illustrates alternative circuitry for performing the same function as the FIG. 3 circuitry but with reduced hardware. In FIG. 5, input signal is applied to a connection 500 from which it is coupled to a one horizontal line period delay element 501 and to the input connections X1 and X4 of the switching circuit 503. Delayed signal from the delay element 501 is reversed in polarity by inverter 502 and coupled to the input connections X2 and X3 of the switching circuit 503. Switching circuit 503, responsive to an operating signal of frequency FH /2, alternately couples input connections X1 and X2 to an output connection S1 for successive line intervals. Switching circuit 503 also alternately couples input connections X3 and X4 to an output connection S2 for successive line intervals. The signals at output connections S1 and S2 respectively conform to signals S1 and S2 in FIG. 4. The signals from connections S1 and S2 quadrature modulate a carrier signal of frequency kfH in elements 306, 307 and 308, the output of which is applied to the modulator 32 (FIG. 2).
The carrier of frequency kfH is phase locked to the horizontal frequency of the video signal and the operating signal FH /2 applied to the multiplexers or switching circuits 301 and 503 is also phase locked to the horizontal frequency. By virtue of switching at fH /2 and the subtractive comb filter function, the energy of the processed auxiliary signal falls in spectral bands at odd multiples of half the line frequency. Modulating the signals S1 and S2 at a frequency kfH translates the signal spectra by an integer multiple of the horizontal frequency. For k=47 the spectra is translated upward in frequency by approximately 0.75 MHz. When the translated signal is single side band (lower band) modulated by the video carrier, the auxiliary signal carrier is located at kfH below the video carrier and the auxiliary signal may be frequency interleaved with the luminance component, by simply additively combining the signals.
FIG. 6 shows the receiving end of the system for transmitting an auxiliary signal in a standard TV signal. It is assumed that the auxiliary signal is a sound signal. In FIG. 6 the transmitted signal is received by an antenna 600 and coupled to a tuner section 601. The RF signal from the tuner is applied to a conventional video processor 602 for generating a visual display. Note that the auxiliary signal, being in the vestigial sideband is substantially attenuated by the Nyquist filter function of conventional picture IF circuitry and thus does not interfere with the picture processing.
The RF signal from the tuner is coupled to conventional sound processing circuitry 603 which extracts and processes the conventionally transmitted sound signal. Audio signals from the circuitry 603 are coupled to a multiplexer 608, the output of which is coupled to sound reproduction apparatus 609. The apparatus 609 may include amplifiers and speakers. The other input to the multiplexer is the auxiliary sound signal which under normal conditions, and being a digital signal, is assumed to be of higher quality than the conventionally transmitted sound signal. The multiplexer 608 is controlled by a SELECT signal which may be manually provided by the user of the receiver or internally generated as a function of, e.g. the signal/noise ratio of the auxiliary signal, the conventional sound signal or both, etc.
The RF signal from the tuner 601 is coupled to an auxiliary IF/detector circuit 604 which is tailored to respond to the vestigial sideband of the transmitted signal. The circuitry 604 produces baseband quadrature modulated auxiliary signal, by for example quadrature detecting the video carrier.
The baseband auxiliary signal is decoded in circuitry 605 responsive to signals of frequency FH /2 and kfH provided by the phase locked loop 606. Decoded auxiliary signal is processed in circuitry 607 and coupled to the multiplexer 608. The processing circuitry 607 may include circuitry to decode, e.g., duo binary signals to parallel stereo signals, and digital-to-analog converters, etc.
An example of the baseband auxiliary decoder 605 is illustrated in FIG. 7. Baseband auxiliary signal from the IF/DETECTOR circuit 604 is applied to connection 700 and coupled to multipliers 702 and 704. The auxiliary signal is multiplied in multipliers 702 and 704 by signals of frequency kfH and quadrature phase provided by the PLL circuit 606. Output signal from multiplier 702 is applied to a low pass filter 706, the output of which is coupled to the input connections X1 and X4 of a multiplexer or switching circuit 710. Output signal from multiplier 704 is applied to a low pass filter 708, the output of which is coupled to the input connections X2 and X3 of the multiplexer 710. The bandwidth of the low pass filters 706 and 708 is selected to pass the frequency components of signals S1 and S2 and is at least not substantially greater than kfH. Letting ω=2πkfH, the received baseband auxiliary signal S(t) can be described by S(t)=S1 (t)cosωt+S2 (t)sinωt. The product provided by the multiplier 702 is equal to S1 (t)cos2 ωt+S2 (t)cosωtsinωt, which can be converted, using trigonometric identities, to the form S1 (t)/2-S1 (t)cos2ωt/2+S2 (t)sin2ωt/2. Only the first term is passed by the filter 706. By similar analysis it can be shown that the signal provided by low pass filter 708 is equal to S2 (t)/2.
The multiplexer 710 alternately couples, at one-half the horizontal line rate, signals S1 /2 and S2 /2 to a one horizontal period delay element 712 and alternately couples the signals S2 /2 and S1 /2 to respective first input connections of an adder 716 and a subtracter 714. The output of delay element 712 is coupled to respective second input connections of the subtracter 714 and the adder 716. Referring to FIG. 4 the signal applied to the delay element 712 is designated S3 and the signal applied to the first input connections of the adder 716 and the subtracter 714 is designated S4. The output of the delay element 712 is designated ODE. The signals output by the adder and the subtracter are designated ADD and SUB, respectively. The output of the subtracter 714 is the decoded auxiliary signal and is formed by effectively averaging the redundant signals of opposite polarity. Note the auxiliary signal, attenuated by a factor of 1/2, may be taken directly from the multiplexer 710 (either S3 or S4), however the averaged signal provided by subtracter 714 is likely to be more accurate in the presence of noise.
If the signal is transmitted without error, the output from the adder 716 will be zero. A nonzero output from adder 716 indicates a transmission error. The output of adder 716 may be monitored and, e.g., threshold detected to provide a control signal for corrective action or adaptive processing. For example, a threshold detected signal from adder 716 may be utilized to provide the SELECT control for multiplexer 608 (FIG. 6). (By threshold detection is meant the generation of a control signal if the level of the error signal from the adder 716 exceeds a predetermined level.)
FIG. 8 illustrates a further auxiliary signal spectral conditioner circuit which may be implemented for element 30 in FIG. 2. FIG. 9 illustrates the inverse circuitry which may be implemented for element 605 in FIG. 6.
In FIG. 8 the angular frequency ω is defined ω+2πnfH /4 where n is a small odd integer. The angular frequency ω0 is defined 2π(P-kfH) where P is the frequency of the video carrier. Four operating signals cos(wt), sin(wt), cos(ω0 t) and sin(ω0 t) are required to generate the auxiliary signal for transmission. These signals are generated in a conventional manner by the PLL 800 and mixer 802 responsive to the horizontal synchronizing signal FH and the video carrier.
The auxiliary signal S(t) is applied to respective input connections of two multiplier circuits 804 and 806. The signal S(t) is multiplied by quadrature phase carriers of frequency, e.g., fH /4. Note that the carrier frequency is, in general, significantly less than the bandwidth of the signal S(t) and thus foldover or aliasing components are generated. However, because the quadrature components are available the aliasing components can be eliminated at the receiver. The signal products from the multipliers 804 and 806 are coupled respectively to subtractive 1-H comb filters 808 and 810. The comb filters 808 and 810 respectively produce the signals Sa and Sb defined by the equations:
However, cosω(t-H)=sin(ωt) and sinω(t-H)=cos(ωt) so that Sa and Sb may be rewritten:
The signals Sa and Sb are respectively coupled to the multiplier circuits 812 and 814 wherein they are multiplied by quadrature phase related signals of angular frequency ω0. The signal products from the multipliers 812 and 814 are summed in the adder 816, producing a modulated carrier Ss which may be added directly to the modulated vestigial sideband video signal. The signal Ss is described by the equation
Ss =Sa cos(ω0 t)+Sb sin(ω0 t)
The auxiliary signal decoder in the receiver (FIG. 9) requires four operating signals designated S5 -S8 defined: ##EQU1## where the angular frequencies ω and ω0 are as defined with respect to the FIG. 8 circuitry. These four signals are generated by conventional methods in the signal generator 900, responsive to the horizontal synchronizing signal FH and the video carrier.
In the receiver RF signal from the tuner is bandpass filtered (to pass the vestigial sideband) and coupled to the auxiliary signal decoder input connection 901. This signal is applied to the respective input connections of multipliers 902, 904, 906 and 908 wherein it is multiplied by the signals S5, S6, S7 and S8, respectively. The signal products generated by the multipliers 902, 904, 906 and 908 are coupled respectively to similar low pass filters 910, 912, 914 and 916. The low pass filters 910-916 attenuate signal frequencies greater than the angular ω0. The design constraint of the filters is that they pass signal frequencies contained in the signal S(t)cos2 ωt.
Output signals from the low pass filters 910 and 912 are coupled to an adder 918. The sum of the signals, S9, provided by adder 918 can be shown to be equal to S9 =1/2[S(t)cos2 ωt-S(t-H)sinωtcosωt+S(t)sin2 ωt+S(t-H)sinωtcosωt] collecting like terms S9 =1/2S(t)[cos2 ωt+S(t)sin2 ωt] or S9 =1/2S(t)[cos2 ωt+sin2 ωt]=S(t)/2
Output signals from the low pass filters 914 and 916 are coupled to the adder 920 which generates a signal S10 that can be shown to equal S10 =S(t-H)/2.
The signal S9 is coupled to a one horizontal line delay element 922, which delays the signal S9 =S(t)/2 and produces a delayed signal S9 '=S(t-H)/2. The signal S9 ' is coupled to respective first input connection of an adder 924 and a subtracter 926. The signal S10 is coupled to respective second input connection of the adder 924 and the subtracter 926. The adder 924 produces the signal S(t-H) which is equivalent to the desired signal delayed by one line interval. The subtracter 926 produces a zero valued signal except when transmission errors occur, in which case it produces an error signal.
Note in FIG. 9 the low pass filters 910-916 may be eliminated and two similar lowpass filters inserted after the adders 918 and 920.
In the claims the signal defined as having a substantially continuous frequency spectrum means a signal which does not have its energy concentrated at intervals of the horizontal frequency of a video signal, and in fact may not have a continuous frequency spectrum. That is, it may have holes and/or peaks in its spectrum.
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|EP0714185A2 *||Nov 21, 1995||May 29, 1996||Deutsche Thomson-Brandt Gmbh||Method for simultaneous transmission of digital audio (DAB) and analog television on the same channel|
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|U.S. Classification||348/484, 348/738, 348/E07.042, 348/485, 348/486|
|International Classification||H04N7/06, H04N7/08, H04N5/38, H04J3/00, H04N7/081|
|Aug 11, 1989||AS||Assignment|
Owner name: GENERAL ELECTRIC COMPANY, A CORP. OF NY
Free format text: ASSIGNMENT OF ASSIGNORS INTEREST.;ASSIGNOR:GIBSON, JAMES J.;REEL/FRAME:005112/0377
Effective date: 19890802
|Mar 28, 1995||FPAY||Fee payment|
Year of fee payment: 4
|Jun 1, 1999||REMI||Maintenance fee reminder mailed|
|Nov 7, 1999||LAPS||Lapse for failure to pay maintenance fees|
|Jan 18, 2000||FP||Expired due to failure to pay maintenance fee|
Effective date: 19991105