|Publication number||US5274274 A|
|Application number||US 07/856,550|
|Publication date||Dec 28, 1993|
|Filing date||Mar 23, 1992|
|Priority date||Mar 23, 1992|
|Also published as||DE69311823D1, DE69311823T2, EP0562397A2, EP0562397A3, EP0562397B1|
|Publication number||07856550, 856550, US 5274274 A, US 5274274A, US-A-5274274, US5274274 A, US5274274A|
|Inventors||Brooks R. Leman, Balu Balakrishnan|
|Original Assignee||Power Integrations, Inc.|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (4), Referenced by (19), Classifications (15), Legal Events (6)|
|External Links: USPTO, USPTO Assignment, Espacenet|
1. Field of the Invention
The present invention relates to electronic power control devices and specifically to MOS-gated devices, such as MOSFET transistors and insulated gate bipolar transistors, that switch high voltages to motors and other loads in half-bridge and full-bridge multiphase configurations.
2. Description of the Prior Art
Digital logic is an almost ideal mechanism for switching power on and off to loads, especially with high-current, high-voltage MOSFET transistors that do the actual switching. However, many loads such as motors and fluorescent lights operate at voltages substantially higher than the five volts direct current (DC) used by most digital logic. Some form of level shifting is required to interface the MOSFET switch that floats at high-voltage and the digital logic that is ground referenced.
FIG. 1 illustrates a half-bridge circuit 10 for driving a fluorescent light 12. A pair of MOSFET transistors 14 and 16 switch their junction between ground and a positive high-voltage potential (+HV). The lower end of light 12 is thus driven between ground and +HV through an impedance matching circuit comprising a capacitor 17 and an inductor 18 An oscillator 19 is connected to a low-side driver 20 which in turn controls the gate of transistor 16 and a high-side driver 22 that controls the gate of transistor 14. When transistor 14 is on, transistor 16 will be off, and vice versa. A logic supply voltage (Vdd) powers low-side driver 20 directly and high-side driver 22 indirectly with the help of a bootstrap diode 24 and a bootstrap capacitor 26. Low-side driver 20 controls high-side driver 22 through a pair of control lines 28 and 30. A comparator in high-side driver 22 will latch the switch transistor 14 on and off according to the relative voltages between lines 28 and 30.
FIG. 2 illustrates the basic functional parts of low-side driver 20 which comprises a inear regulator 40, an inverter 42 with hysteresis, an under-voltage lockout 44, a buffer with hysteresis 46, a NAND-gate 48, a pulse circuit 50, a pair of transistors 52 and 54, and an output inverter driver 56 which controls the gate of transistor 16. An input 58 receives a control signal that is combined in NAND-gate 48 with an under-voltage signal from lockout 44. If the logic power Vdd falls below a predetermined threshold, driver 56 will be prevented from turning transistor 16 on. An input 60 receives an inverted control signal that will turn transistor 14 on and off by pulsing either transistor 52 or transistor 54 on and the other being off. Which line, 28 or 30, is lower than the other will be sensed by high-side driver 22 and used to ultimately control the gate of transistor 14.
FIG. 3 illustrates high-side driver 22 which comprises a linear regulator 70, a discriminator 72, an under-voltage lockout 74, an AND-gate 76, a flip-flop 78, an output driver 80, a pair of constant current sources 82 and 84, a pair of transistors 86 and 88, a pair of Zener diodes 90 and 92, and a pair of input pull-up resistors 94 and 96. An output 98 is connected to driver 80 and the gate of transistor 14. A reference common 99 connects to the source of transistor 14 and can swing from below ground in circuit 10 to above +HV, in some cases. Diode 24 takes advantage of these swings to provide a supply voltage Vddh. If the supply voltage Vddh falls below a predetermined threshold, driver 80 will be prevented from turning transistor 14 on. Transistors 86 and 88 in a common source configuration present a high-impedance comparator input to control lines 28 and 30. If the voltage on line 30 is more negative than a predetermined threshold, e.g. Vddh-1.5 volts, and transistor 52 (FIG. 2) is off and transistor 54 is on, then the set (S) input of flip-flop 78 will go true, turning transistor 14 (FIG. 1) off. If the voltage on line 28 is more negative than the predetermined threshold, and transistor 54 (FIG. 2) is off and transistor 52 is on, then the reset (R) input of flip-flop 78 will go true, turning transistor 14 on. Table I summarizes the control function. Symbols S, R and Q are the set, reset and output, respectively, of flip-flop 78. The asterisk in the first two columns indicates negative true logic, HIGH=more negative input than threshold voltage, LOW=less negative than threshold voltage.
TABLE I______________________________________Line 28* Line 30* S R Q______________________________________HIGH LOW HIGH LOW HIGHLOW HIGH LOW HIGH LOWHIGH HIGH LOW LOW No ChangeLOW LOW LOW LOW No Change______________________________________
A problem develops in discriminator 72 with 5 such a simple input and logic. Noise on lines 28 and 30 can easily be induced and proper circuit 10 operation depends on a high degree of common mode noise rejection. If an imbalance develops between lines 28 and 30, such as can happen with unequal stray line capacitances and high frequency environments, false triggering of transistor 14 can occur. These false triggers can be very serious if they occur while transistor 16 is on, because +HV will momentarily find a short path to ground through transistor 14, causing a high current pulse.
A high-side driver is needed that is immune to false triggering caused by rapid common mode slewing of the control lines. An improved threshold region of the comparators is needed to prevent a slight mismatching of the control lines to trigger an unintended change of state.
It is therefore an object of the present invention to provide a power control system that prevents false triggering of high-side, floating switch control transistors.
Briefly, an embodiment of the present invention is a high-side driver comprising a pair of differential input controls each of which are coupled to a pair of comparators having first and second thresholds set at Vddh-1.5 volts and Vddh-2.5 volts, respectively. A logic block in front of a set-reset flip-flop recognizes only signals on the control lines where one is less than the Vddh-1.5 volt threshold and the other exceeds the Vddh-2.5 volt threshold. If signals on either or both of the control lines are between Vddh-1.5 volts and Vddh-2.5 volts, the logic block will prevent a change of state of the flip-flop which controls a high-voltage switch transistor connected to a load. The high-side driver further includes an under-voltage lockout to prevent false operation of the high-voltage switch transistor during the initial power up phase.
An advantage of the present invention is that a high-side driver is provided that has an increased level of common mode rejection on the control inputs.
Another advantage of the present invention is that a high-side driver is provided that substantially eliminates false triggering of the output by high-frequency and high-voltage switching of a load.
Another advantage of the present invention is that a high-side driver is provided that is less sensitive to control line routing and device placement on a printed circuit board.
Another advantage of the present invention is that a high-side driver can be implemented with a small number of circuit elements.
These and other objects and advantages of the present invention will no doubt become obvious to those of ordinary skill in the art after having read the following detailed description of the preferred embodiments which are illustrated in the various drawing figures.
FIG. 1 is a schematic block diagram of a half-bridge power control system with a prior art high-side and low-side drivers;
FIG. 2 is a schematic block diagram of the prior art low-side driver of FIG. 1;
FIG. 3 is a schematic block diagram of the prior art high-side driver of FIG. 1;
FIG. 4 is a schematic block diagram of a dual-threshold high-side driver, according to a first embodiment of the present invention;
FIG. 5 is a schematic diagram of a dual-threshold high-side driver, according to a second embodiment of the present invention; and
FIG. 6 is a schematic diagram of a dual-threshold high-side driver, according to an alternative embodiment of the driver of FIG. 5.
In FIG. 4, an embodiment of the present invention is a high-side transistor driver 100 comprising a linear regulator 102, a four-input logic block 104, an under-voltage lockout 106, an AND-gate 108, a flip-flop 110, an output driver 112, a set of four constant current sources 114-117, a set of four transistors 118-121, a pair of Zener diodes 122 and 124, and a pair of input pull-up resistors 126 and 128. An output 130 couples driver 112 to the gate of an external high-voltage switch transistor (e.g., transistor 14 in FIG. 1). A reference 132 connects to the source of the external switch transistor. A pair of control input lines 134 and 136 receive a differential signal from a low side driver (e.g., low-side driver 20 in FIG. 1). Transistors 120 and 119, together with constant current sources 116 and 115, form a 1.5 volt comparator function for inputs "A1" and "B1" of logic block 104, respectively. Transistors 121 and 118 with constant current sources 117 and 114, form a 2.5 volt comparator function for inputs "A2" and "B2" of logic block 104, respectively. Input "A1" will be true whenever the voltage on line 134 drops more than 1.5 volts more negative than Vddh, which serves as a reference. Input "A2" will be true whenever the voltage on line 134 drops more than 2.5 volts more negative than Vddh. Input "B1" will be true whenever the voltage on line 136 drops more than 1.5 volts more negative than Vddh. Input "B2" will be true whenever the voltage on line 136 drops more than 2.5 volts more negative than Vddh. Logic block 104 is such that it recognizes only signals on the control lines 134 and 136 where one is less than the Vddh-1.5 volt threshold and the other exceeds the Vddh-2.5 volt threshold. If signals on either or both of the control lines 134 and 136 are between Vddh-1.5 volts and Vddh-2.5 volts, or both are less negative than Vddh-1.5 volts or both are more negative than Vddh-2.5 volts, logic block 104 will prevent a change of state of flip-flop 110. Table II summarizes the logic states that result for various combinations of input voltages (X) on line 134 and input voltages (Y) on line 136. These voltages are negative, with respect to Vddh. The set, reset and output of flip-flop 110 are "S", "R" and "Q", respectively. It is assumed in Table II that an under-voltage condition does not exist, so "R" is received only from logic block 104. The asterisk in the first two columns of Table II is meant to call attention to the fact that voltage threshold one (VT1) represents Vddh-1.5 volts and voltage threshold two (VT2) represents Vddh-2.5 volts.
TABLE II__________________________________________________________________________Line 134* Line 136* A1 A2 B1 B2 S R Q__________________________________________________________________________X > VT2 Y < VT1 1 1 0 0 1 0 1X < VT1 Y > VT2 0 0 1 1 0 1 0X > VT2 VT1 < Y < VT2 1 1 1 0 0 0 n/cVT1 < X < VT2 Y > VT2 1 0 1 1 0 0 n/cX > VT2 Y > VT2 1 1 1 1 0 0 n/cX < VT1 Y < VT1 0 0 0 0 0 0 n/cVT1 < X < VT2 VT1 < Y < VT2 1 0 1 0 0 0 n/c__________________________________________________________________________ "n/c" = no change in state.
A second embodiment of the present invention is illustrated in FIG. 5. A dual-threshold discriminator 150 is functionally equivalent to high-side driver 100, except that a linear regulator and under-voltage detector are not included. These functions can be provided externally. Discriminator 150 comprises a plurality of input protection Zener diodes 152, a pair of clamping diodes 154 and 155 with a pair of dropping resistors 156 and 157, a pair of series input resistors 158, a set of four comparison transistors 160-163, a set of four constant current sources 164-167, a set of four logic protection Zener diodes 168-171, a logic block 172, a flip-flop 174, a NAND-gate 176, and a pair of output inverters 178 and 180. Logic block 172 includes a plurality of inverters 182, an AND-gate 184 and a NAND-gate 186. Flip-flop 174 is constructed of a pair of NOR-gates 188 and 190. A dual-input control signal is received on a pair of lines 192 and 194 and an output line 196 controls the gate of an external high-side, high-voltage switch transistor that has its source connected to a common 197. An under-voltage control signal is received on an input 198. Power (Vddh) to operate discriminator 150 is supplied to a terminal 199.
The two different threshold voltages above are obtained by adjusting the relative sizes of transistors 160-163. Alternatively, transistors 160-163 can be the same size and the current through constant-current sources 164-167 can be individually adjusted to set the two thresholds.
A still further alternative is to use voltage taps on resistors 156 and 157, as shown in FIG. 6, for a discriminator 150' which is similar to discriminator 150. The gate of transistor 163 has a tap on resistor 157. The gate of transistor 161 is similarly tapped on resistor 156. Transistors 161 and 163 with constant current sources 165 and 167 form the 1.5 volt threshold comparator.
Although the present invention has been described in terms of the presently preferred embodiments, it is to be understood that the disclosure is not to be interpreted as limiting. Various alterations and modifications will no doubt become apparent to those skilled in the art after having read the above disclosure. For example, in FIG. 4, the circuitry between lines 134 and 136 and driver 112 could be replaced by an op-amp configured to accept differential voltage inputs and that has a small amount of the output signal fed back to the non-inverting terminal. A differential hysteris effect is created in which a difference of voltage on control lines 134 and 136 must exceed some minimum set by the amount of positive feedback in order for the output to switch state. Linear circuits could also be used in a configuration that compares the control lines 134 and 136 independently to the two thresholds. However, the current state-of-the-art is such that such linear circuits are limited in their frequency ranges and add a level of complexity that increases the costs of manufacturing. The limitations of such configurations, however, may improve with future developments in those areas. Accordingly, it is intended that the appended claims be interpreted as covering all alterations and modifications as fall within the true spirit and scope of the invention.
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|U.S. Classification||327/74, 327/401, 327/427, 327/392|
|International Classification||H03K17/687, H03K17/30, H03K17/16, H05B41/24, H02M1/10|
|Cooperative Classification||H03K17/161, H03K17/687, H03K17/302|
|European Classification||H03K17/30B, H03K17/16B, H03K17/687|
|Mar 23, 1992||AS||Assignment|
Owner name: POWER INTEGRATIONS, INC. A CORP. OF CALIFORNIA,
Free format text: ASSIGNMENT OF ASSIGNORS INTEREST.;ASSIGNORS:LEMAN, BROOKS R.;BALAKRISHNAN, BALU;REEL/FRAME:006068/0609
Effective date: 19920323
|Mar 14, 1995||AS||Assignment|
Owner name: IMPERIAL BANK, CALIFORNIA
Free format text: SECURITY INTEREST;ASSIGNOR:POWER INTEGRATIONS, INC.;REEL/FRAME:007470/0543
Effective date: 19950215
Owner name: MAGNETEK, INC., CALIFORNIA
Free format text: LICENSE;ASSIGNOR:POWER INTEGRATIONS, INC.;REEL/FRAME:007388/0219
Effective date: 19930219
|Jul 19, 1996||AS||Assignment|
Owner name: HAMBRECHT & QUIST TRANSITION CAPITAL, INC., CALIFO
Free format text: SECURITY AGREEMENT;ASSIGNOR:POWER INTEGRATIONS, INC.;REEL/FRAME:008040/0236
Effective date: 19960522
|Jun 26, 1997||FPAY||Fee payment|
Year of fee payment: 4
|Jun 27, 2001||FPAY||Fee payment|
Year of fee payment: 8
|Jun 28, 2005||FPAY||Fee payment|
Year of fee payment: 12