Publication number | US7292185 B2 |
Publication type | Grant |
Application number | US 11/243,112 |
Publication date | Nov 6, 2007 |
Filing date | Oct 4, 2005 |
Priority date | Oct 4, 2005 |
Fee status | Paid |
Also published as | US20070075896 |
Publication number | 11243112, 243112, US 7292185 B2, US 7292185B2, US-B2-7292185, US7292185 B2, US7292185B2 |
Inventors | Michael L. Whitehead, Cary Davis, Dale R. Scott |
Original Assignee | Csi Wireless Inc. |
Export Citation | BiBTeX, EndNote, RefMan |
Patent Citations (19), Non-Patent Citations (5), Referenced by (29), Classifications (5), Legal Events (5) | |
External Links: USPTO, USPTO Assignment, Espacenet | |
The invention relates generally to precision attitude measuring systems. More specifically, the invention relates to systems that utilize Global Navigation Satellite System (GNSS) signals to infer differential path length of carrier signals arriving at two or more antennas to ultimately determine attitude.
The determination of the orientation of an object's axes relative to a reference system is often of interest. Depending on the application, the orientation and reference system may be in two dimensions (2D) or in three dimensions (3D). In the case of two-dimensional systems, terms such as azimuth, heading, elevation, pitch, and inclination may be used in place of attitude.
There are many techniques in use to measure 2D and 3D attitude. Common techniques include using a magnetic compass to reference the object of interest to the local gravitational field, optical techniques to reference the object of interest to an earth-based or star-based reference frame, accelerometers to measure relative attitude or changes in attitude, and optical and mechanical gyroscopes for also measuring relative attitude. The merits of each technique are best judged according to the specific application or use. Likewise, each technique also exhibits disadvantages that may include accuracy, cost, and ease of use.
Recently, attitude determination using highly accurate space-based radio navigation systems has become possible. Such a radio navigation system is commonly referred to as a Global Navigation Satellite System (GNSS). A GNSS includes a network of satellites that broadcast radio signals, enabling a user to determine the location of a receiving antenna with a high degree of accuracy. To determine the attitude of an object, it is simply necessary to determine the position of two or more receiving antennas that have known placements relative to an object. Examples of GNSS systems include Navstar Global Positioning System (GPS), established by the United States; Globalnaya Navigatsionnay Sputnikovaya Sistema, or Global Orbiting Navigation Satellite System (GLONASS), established by the Russian Federation and similar in concept to GPS; and Galileo, also similar to GPS but created by the European Community and slated for full operational capacity in 2008.
Should it be necessary to improve the accuracy, reliability, or confidence level of an attitude or position determined through use of a GNSS, a Satellite-Based Augmentation System (SBAS) may be incorporated if one that is suitable is available. There are several public SBAS that work with GPS. These include Wide Area Augmentation System (WAAS), developed by the United States' Federal Aviation Authority, European Geostationary Navigation Overlay Service (EGNOS), developed by the European Community, as well as other public and private pay-for-service systems.
Currently the best-known of the available GNSS, GPS was developed by the United States government and has a constellation of 24 satellites in 6 orbital planes at an altitude of approximately 26,500 km. The first satellite was launched in February 1978. Initial Operational Capability (IOC) for the GPS was declared in December 1993. Each satellite continuously transmits microwave L-band radio signals in two frequency bands, L1 (1575.42 MHz) and L2 (1227.6 MHz). The L1 and L2 signals are phase shifted, or modulated, by one or more binary codes. These binary codes provide timing patterns relative to the satellite's onboard precision clock (synchronized to other satellites and to a ground reference through a ground-based control segment), in addition to a navigation message giving the precise orbital position of each satellite, clock correction information, and other system parameters.
The binary codes providing the timing information are called the C/A Code, or coarse acquisition code, and the P-code, or precise code. The C/A Code is a 1 MHz Pseudo Random Noise (PRN) code modulating the phase of the L1 signal, and repeating every 1023 bits (one millisecond). The P-Code is also a PRN code, but modulates the phase of both the L1 and L2 signals, and is a 10 MHz code repeating every seven days. These PRN codes are known patterns that can be compared to internal versions in the receiver. The GNSS receiver is able to compute an unambiguous range to each satellite by determining the time-shift necessary to align the internal code to the broadcast code. Since both the C/A Code and the P-Code have a relatively long “wavelength”—approximately 300 meters (or 1 microsecond) for the C/A Code, and 30 meters (or 1/10 microsecond) for the P-Code, positions computed using them have a relatively coarse level of resolution.
To improve the positional accuracy provided by use of the C/A Code and the P-Code, a receiver may take advantage of the carrier component of the L1 or L2 signal. The term “carrier”, as used herein, refers to the dominant spectral component remaining in the radio signal after the spectral content resulting from the modulating PRN digital codes has been removed (e.g., from the C/A Code and the P-Code). The L1 and L2 carrier signals have wavelengths of about 19 centimeters and 24 centimeters, respectively. The GPS receiver is able to track these carrier signals and measure the carrier phase to a small fraction of a complete wavelength, permitting range measurement to an accuracy of less than a centimeter.
A final technique to improve accuracy, and which shall be seen to be of key interest here, is the technique of differencing GPS range measurements—known as Differential GPS (DGPS). The combination of DGPS with precise measurements of carrier phase leads to differential position accuracies of less than one centimeter root-mean-squared (i.e., centimeter-level positioning). Such accuracies are sufficient to determine the attitude of an object with 2 or more GPS GNSS antennas, typically spaced from 0.2 meters to 2 meters apart.
Therefore, what is needed in the art is a system that utilizes Global Navigation Satellite System (GNSS) signals to infer differential path length of carrier signals arriving at two or more antennas to ultimately determine attitude while leveraging the advantages of geometry constraints of the antennas attached to a rigid body, and does so with measurements from all antennas processed simultaneously and optimally.
An exemplary embodiment of the invention features a method of attitude determination that is effective and completely exploits geometry constraints of the antennas attached to a rigid body, and preferably does so with measurements from all antennas processed simultaneously and optimally. This occurs both during the solution of the ambiguities and during normal operation of the attitude device.
Disclosed herein in an exemplary embodiment is a method for determining at least one attitude angle of a rigid body. The method comprising: receiving a plurality of Global Navigation Satellite System (GNSS) satellite signals with a plurality of antennas; establishing at least one pair of antennas such that each antenna of the plurality of antennas is included in at least one antenna pair; computing single- or double-difference phases corresponding to one or more GNSS satellites for each of the pairs of antennas; and constructing a single Differential Carrier Phase Attitude (DCPA) equation based on known geometry constraints of each of the pairs of antennas. The method also includes determining a solution for the DCPA equation based on a cost function, the solution yielding at least one integer ambiguity value and the at least one attitude angle.
Also disclosed herein in an exemplary embodiment is a system for determining at least one attitude angle of a rigid body. The system comprising: a plurality of antennas disposed on the rigid body, the plurality of antennas exhibiting known relative geometries and receptive to a plurality of Global Navigation Satellite System (GNSS) satellite signals. The plurality antennas partitioned into at least one pair of antennas such that each antenna of the plurality of antennas is included in at least one antenna pair. The system also includes: a receiver in operable communication with the plurality of antennas and configured to receive the GNSS satellite signals therefrom. The receiver is configured to: compute single- or double-difference phases corresponding to one or more GNSS satellites for each of the at least one pair of antennas, construct a single Differential Carrier Phase Attitude DCPA equation based on constraints from the known relative geometries of each of the pairs of antennas, and determine a solution for the DCPA equation based on a cost function, the solution yielding at least one integer ambiguity value and the at least one attitude angle.
Further disclosed herein in an exemplary embodiment is a system for determining at least one attitude angle of a rigid body. The system comprising: means for receiving a plurality of Global Navigation Satellite System (GNSS) satellite signals with a plurality of antennas; means for establishing at least one pair of antennas such that each antenna of the plurality of antennas is included in at least one antenna pair; and means for computing single- or double-difference phases corresponding to one or more GNSS satellites for each of the pairs of antennas. The system also includes means for constructing a single Differential Carrier Phase Attitude (DCPA) equation based on known geometry constraints of each of the pairs of antennas; and means for determining a solution for the DCPA equation based a cost function, the solution yielding at least one integer ambiguity value and the at least one attitude angle.
Also disclosed herein in yet another exemplary embodiment is a storage medium encoded with a machine readable computer program code, the code including instructions for causing a computer to implement the above-mentioned method for determining at least one attitude angle of a rigid body.
Further, in yet another exemplary embodiment, there is disclosed herein a computer data signal, the computer data signal comprising instructions for causing a computer to implement the above-mentioned method for determining at least one attitude angle of a rigid body.
Additional features, functions, and advantages associated with the disclosed methodology will be apparent from the detailed description which follows, particularly when reviewed in conjunction with the figures appended hereto.
To assist those of ordinary skill in the art in making and using the disclosed embodiments, reference is made to the appended figures, wherein like references are generally numbered alike in the several figures:
An exemplary embodiment of invention features a method and system for attitude determination that is effective and completely exploits geometry constraints of the antennas attached to a rigid body, and does so with measurements from all antennas processed simultaneously and optimally. This occurs both during the solution of the ambiguities, and during normal operation of the attitude device. In contrast, the methods of prior art separate antennas into pairs, then solve single-difference or double-difference ambiguities for each pair independently. In one such method, geometry constraints are taken into account only after the ambiguities are solved to validate the results. In another method, the ambiguities are solved over an antenna pair of a substantially short baseline and the resulting solution is then used to narrow the search for ambiguities over another antenna pair of longer baseline.
A preferred embodiment of the invention, by way of illustration, is described herein as it may be applied to attitude determination of a rigid body with known geometry constraints. While a preferred embodiment is shown and described by illustration and reference to attitude determination, it will be appreciated by those skilled in the art that the invention is not limited to attitude determination alone, and may be applied to attitude determination, control systems, navigation and the like.
It will further be appreciated that, while particular sensors, antennas, receivers and the like nomenclature associated therewith are enumerated to describe an exemplary embodiment, such terminology is utilized and described for illustration only and are not limiting. Numerous variations, substitutes, and equivalents will be apparent to those contemplating the disclosure herein.
In order to perform the prescribed functions and desired processing, as well as the computations therefore (e.g., the attitude determination processes, and the like), the receiver 108 may include, but not be limited to, a processor(s), computer(s), memory, storage, register(s), timing, interrupt(s), communication interface(s), and input/output signal interfaces, and the like, as well as combinations comprising at least one of the foregoing. For example, receiver 108 may include signal interfaces to enable accurate down-conversion and digitally sampling and tracking of satellite signals as needed to facilitate extracting the various timing and navigation information, including, but not limited to, the phase of the PRN code timing pattern. Additional features of the system 100, receiver 108 and the like, are thoroughly discussed herein.
One exemplary embodiment of an attitude determining system 100 shown in
A synchronization signal 214, denoted as sync, sent by the master tracking device 202 to the slave tracking devices, 203 and 204 allows the master tracking device 202 and slave tracking devices 203, 204 to measure the code and carrier phase of each satellite signal 104 simultaneously. Furthermore, the RF down conversion within each tracking device 202, 203, and 204 and the sampling of data by each device is done using a common clock signal, 220. When a single-difference phase observation is formed by subtracting the carrier (or code) phase measured by one tracking device with that measured by another tracking device for the same satellite, the portion of the phase due to the receiver's clock error is essentially eliminated in the difference. Thereafter, all that remains of the single-difference clock error is a small, nearly constant bias that is due to different effective RF path lengths (possibly resulting from different cable lengths, slightly different filter group-delays, and the like). Consequently, the clock error may be estimated infrequently compared to other more important quantities such as heading, pitch, or roll. During the times that the clock error is not estimated the attitude device can produce an output using one fewer satellite than a system that must continually estimate clock error. Or, if a Kalman filter is utilized, the process noise for the clock state may be lowered substantially allowing the Kalman filter to strengthen its estimate of the other states such as the angles of attitude. Finally, cycle slips are easier to detect since clock jumps can be ruled out.
Referring again to
Turning now to
Considering
Mathematically, the following equation holds for either
{right arrow over (R)} _{SB} ={right arrow over (R)} _{SA} +{right arrow over (R)} _{AB}
The geometric distance from a satellite S to an antenna A is the magnitude of the vector {right arrow over (R)}_{SA }and this magnitude, denoted {right arrow over (R)}_{SA}, can be computed with a dot product as
R _{SA} =∥{right arrow over (R)} _{SA} ∥={right arrow over (R)} _{SA} ·{right arrow over (U)} _{SA}
Where {right arrow over (U)}_{SA }is a unit vector in the direction of the vector {right arrow over (R)}_{SA}. That is
where
Again, referring to
R _{SB} =∥{right arrow over (R)} _{SB}∥=({right arrow over (R)} _{SA} +{right arrow over (R)} _{AB})·{right arrow over (U)} _{SB}
where {right arrow over (R)}_{AB }is the baseline vector from point A to point B.
In
{right arrow over (U)}_{S}={right arrow over (U)}_{SA}={right arrow over (U)}_{SB}
It may then be shown that
R _{SB} −R _{SA} ={right arrow over (R)} _{AB} ·{right arrow over (U)} _{S}
The range R_{SA }from satellite S to point A may be expressed in terms of the carrier phase φ_{SA}. This carrier phase is measured by the tracking device associated with an antenna at point A and is related to {right arrow over (R)}_{SA }by the following equation.
φ_{SA} =R _{SA} +Clk _{A} −Clk _{S} +Atmos+N _{SA} +Noise
where each of the terms in the above equation are preferably expressed in units of carrier cycles and these terms are:
A similar equation can be written for the carrier phase φ_{SB }that is measured by the tracking device connected to antenna B and receiving a signal from satellite S. Since the two antennas are near to each other, the atmospheric effect on the carrier phase, Atmos, is essentially the same for both φ_{SA }and φ_{SB}. Ignoring noise, the difference between the two phases is thus:
φ_{SB}−φ_{SA} =R _{SB} −R _{SA} +Clk _{B} −Clk _{A} +N _{SB} −N _{SA}
or
φ_{SAB} =R _{SB} −R _{SA} +Clk _{AB} +N _{SAB}.
The definitions φ_{SAB}=φ_{SB}−_{SA}, N_{SAB}=N_{SB}−N_{SA }and Clk_{AB}=Clk_{B}−Clk_{A }have been made not only to simply the equation, but also because it is these differential quantities, rather than their individual constituents, that are beneficial to the methods outlined herein for the exemplary embodiments. It is noteworthy to appreciate that the ambiguity difference, N_{SAB}, is still an integer since it is the difference between two integers.
Using the relationship R_{SB}−R_{SA}={right arrow over (R)}_{AB}·{right arrow over (U)}_{S }the differential phase measurement may be expressed in terms of the baseline vector, {right arrow over (R)}_{AB}, that extends from point A to point B.
φ_{SAB} ={right arrow over (R)} _{AB} ·{right arrow over (U)} _{S} +Clk _{AB} +N _{SAB}
The above equation is termed a “single-difference” equation. It is an equation that is used extensively in the attitude determining process. Similar single-difference equations hold for each satellite whose signal it received at antennas A and B and tracked by the receiver. Furthermore, “double-difference” equations that effectively eliminate the clock term Clk_{AB }are also readily derived. For example, if the subscript S is replaced with a number representing the particular satellite, then for satellite #1 and satellite #2 the differential phase equations may be written as:
φ_{1AB} ={right arrow over (R)} _{AB} ·{right arrow over (U)} _{1} +Clk _{AB} +N _{1AB}
and
φ_{2AB} ={right arrow over (R)} _{AB} ·{right arrow over (U)} _{2} +Clk _{AB} +N _{2AB}
Subtracting the equation for satellite 2 from the equation for satellite 1 yields a “double-difference” equation:
φ_{1AB}−φ_{2AB} ={right arrow over (R)} _{AB}·({right arrow over (U)} _{1} −{right arrow over (U)} _{2})+(N _{1AB} −N _{2AB})
or
φ_{1AB}−φ_{2AB} ={right arrow over (R)} _{AB} ·{right arrow over (W)} _{12} +N _{12AB}
where the vector {right arrow over (W)}_{12}=({right arrow over (U)}_{1}−{right arrow over (U)}_{2}) is no longer a unit vector, but the double-difference ambiguity N_{12AB}=(N_{1AB}−N_{2AB}) is still an integer and the clock term Clk_{AB }is gone. For compactness, the following notation is introduced for the double difference phase involving two satellites designated as satellites ‘i’ and ‘j’.
φ_{AB} ^{ij}=φ_{iAB}−φ_{jAB}
Hence:
φ_{AB} ^{12} ={right arrow over (R)} _{AB} ·{right arrow over (W)} _{12} +N _{12AB}
Continuing now with
The attitude of the rigid-body 500 is completely specified by three angles of heading (sometimes also called yaw), pitch, and roll. These angles are labeled in
A purpose of the attitude determining system 100 is to compute Ψ,θ, and φ. Although two baseline vectors have been shown in
The baseline vectors may be expressed in an earth-fixed coordinate system 508 by using matrix transformations that are well understood in the art. These may be written as:
{right arrow over (R)} _{AB} =[T(Ψ,θ,φ)]{right arrow over (R)} _{AB} ^{Body}
{right arrow over (R)} _{AC} =[T(Ψ,θ,φ)]{right arrow over (R)} _{AC} ^{Body}.
Here [T(Ψ,θ,φ)] is a 3×3 matrix transforming baseline vectors that are expressed in a body-fixed coordinates, such as {right arrow over (R)}_{AB} ^{Body }or {right arrow over (R)}_{AC} ^{Body}, into an earth-fixed coordinate system. In earth-fixed coordinates, the superscript ‘Body’ is dropped from the notation and thus {right arrow over (R)}_{AB }and {right arrow over (R)}_{AC }are the earth-fixed representation of {right arrow over (R)}_{AB} ^{Body }and {right arrow over (R)}_{AC} ^{Body}. The matrix [T(Ψ,θ,φ)] can be computed as
Using what has been developed so far, the following double-difference equation for satellites i and j can be written with respect to the baseline vector from A to B.
φ_{AB} ^{ij} ={right arrow over (W)} _{ij} [T(Ψ,θ,φ)]{right arrow over (R)} _{AB} ^{Body} +N _{ijAB}
Similarly, for the baseline vector from A to C, the following double-difference equation holds
φ_{AC} ^{ij} ={right arrow over (W)} _{ij} [T(Ψ,θ,φ)]{right arrow over (R)} _{AC} ^{Body} +N _{ijAC}
Let ‘M’ specify the number of double-difference phase observations available for the antenna pair AB and let {right arrow over (φ)}_{AB }be a vector comprising these M double-difference phase observations. Also, let [W_{AB}] denote a 3×M matrix with rows made up of the individual {right arrow over (W)}_{ij }vectors associated with each double-difference phase observation contained within {right arrow over (φ)}_{AB}, and let {right arrow over (N)}_{AB }be the vector of M double-difference ambiguities for {right arrow over (φ)}_{AB}. Similarly, for the vector pair AC, define the double-difference phase vector {right arrow over (φ)}_{AC}, an ambiguity vector {right arrow over (N)}_{AC}, and a matrix [W_{AC}]. We note that [W_{AB}] and [W_{AC}] likely have rows in common since each depends only on the satellites chosen to form the double-difference observations and does not depend on baseline geometry.
Double-difference equations for baselines AB and AC can be represented in matrix form as:
For an arbitrary number of antenna baselines, the above equation can be written more compactly and more generally as:
{right arrow over (φ)}=[W _{d} ∥T _{d}(Ψ,θ,φ)]{right arrow over (V)}+{right arrow over (N)}
This equation shall be termed the Differential Carrier Phase Attitude (DCPA) equation. In the DCPA equation, {right arrow over (φ)} is a vector that includes all double-difference carrier phase measurements taken across all baseline vectors, [W_{d}] is a corresponding block-diagonal matrix consisting of blocks such as [W_{AB}] and [W_{AC}], [T_{d}(Ψ,θ,φ)] is a block-diagonal set of rotation matrices, (where each block is the exact same 3×3 matrix, [T(Ψ,θ,φ)]), {right arrow over (V)} is the concatenation of all body-fixed baseline vectors into a single column vector, and {right arrow over (N)} is the double-difference ambiguities associated with {right arrow over (φ)}. At this point, it is worth mentioning that {right arrow over (φ)} is computed from measured carrier phases, [W_{d}] is readily determined from the user's location and the broadcast satellite locations, and {right arrow over (V)} is a set of vectors whose scalar values are known, constant, and depend on the geometric arrangement of antennas within the body-fixed coordinate system. What remains to be solved are the attitude angles Ψ,θ,φ and the ambiguities {right arrow over (N)}.
Use of the DCPA equation is advantageous since it fully incorporates knowledge of geometry constraints relating to the arrangement of the antennas in order to minimize the number of unknown variables. This ultimately strengthens the solution of the equation. Regardless of the number of antenna baselines, the DCPA equation contains a maximum of three independent variables, Ψ,θ,φ plus the ambiguities {right arrow over (N)} (only two independent variables for a single baseline). Conversely, existing approaches treat each baseline separately, introducing unknown attitude angles (or differential positions) for each baseline, and then take antenna geometry into account after separately solving the individual baselines.
Although the DCPA equation was derived using double-difference phase observations, it is not difficult to reformulate the DCPA equation using single- rather than double-difference observations. When doing so, clock terms arise for each pair of baselines. Nevertheless, the clock terms may be solved in addition to Ψ,θ,φ and the ambiguities {right arrow over (N)}. Or, the clock terms may be known in advance from past solutions.
The single-difference form of the DCPA equation is similar in structure to the double-difference form of the equation except that the differential phase vector {right arrow over (φ)} consists of single-difference phase observations. There are several other differences as well. For example, each 3×1 body-fixed vector comprising the vector {right arrow over (V)} is appended with a clock term, and thus becomes a 4×1 vector. Furthermore, each rotation matrix block within [T_{d}(Ψ,θ,φ)] is changed accordingly from 3×3 matrix to 4×4 matrix with the original 3×3 matrix in the upper left-hand corner and 1 in the lower right diagonal. For example, if the baseline is designated AB, the body-fixed vector for the single-difference DCPA equation takes the form:
and the rotation matrix becomes a 4×4 rotation matrix for single-difference DCPA equation:
where {right arrow over (0)} is a 3×1 matrix of zeroes.
Finally, the rows of the individual block matrices, such as [W_{AB}] are replaced with the unit vectors to the satellite from which the single-difference applies and a 4^{th }column is added that is filled with ones. For example, [W_{AB}] would take a form such as:
where {right arrow over (U)}_{1 }through {right arrow over (U)}_{M }are unit vectors.
Generally, it is preferable to use the single-difference form of the DCPA equation when the clock terms are already known. It is also preferable to use the single-difference form of the DCPA equation in situations that the clock terms might drift slowly and ambiguities are already known. Notably, the single-difference DCPA has one more independent phase observation available than does its double-difference counterpart since one independent observation is used up in the double-differencing. However, it is noteworthy to appreciate that when solving ambiguities without advanced knowledge of clock terms, the double-difference equation is generally preferred.
In order to fully exploit the power of the DCPA equation, the antenna baseline pairs are chosen so that each antenna is in at least one baseline pair. Use of redundant baseline pairs without increasing the number of antennas, while possible, is unlikely to yield added benefit. A redundant baseline pair is one whose baseline vector can be computed as the sum or difference of previously chosen baseline pairs. For example, with three antennas, such as shown in
Turning now to
Turning now to
{right arrow over (W)} _{12} ={right arrow over (U)} _{1} −{right arrow over (U)} _{2}
Changes in the antenna location 705 appear as a change in the double-difference phase to the extent that the change in location is along a line 710 that is parallel to {right arrow over (W)}_{12}. More precisely, the dot product of the antenna's displacement with {right arrow over (W)}_{12 }directly shows up in the double-difference phase. In the reverse sense, an integer change in the double-difference phase will appear as a displacement of the antenna along the line 710. The displacement will be proportional to the carrier wavelength, λ, and inversely proportional to the magnitude of {right arrow over (W)}_{12}. For the sake of analysis and visualization, it is therefore advantageous to imagine that a satellite 720 exists at a location along the line 710 and that it is broadcasting a carrier signal of wavelength λ/∥{right arrow over (W)}_{12}∥. Double-difference ambiguity fronts, 721 and 722, are shown accordingly and are separated by a distance of λ/∥{right arrow over (W)}_{12}∥. It is evident that an integer change in the double-difference carrier phase will cause an apparent change in the antenna location and this location will reside on one of the ambiguity fronts shown.
In
The antenna pair (823,822) with baseline 825 also has only one intersection 828 of ambiguity fronts that lies on the circle. The intersection 842 is not on the circle as it was in the case of antenna pair (823, 821). Thus, the correct set of ambiguities and heading can be uniquely determined for the antenna pair (823,822). Furthermore, when solving the DCPA equation for both pairs of antennas simultaneously, all sets of ambiguities along with the heading angle 832 are uniquely determined. The combination of geometrical constraints, such as the fixed angle 831 and fixed baselines 824 and 825 along with a finite number of ambiguity front intersections dictates exactly one solution to the DCPA equation.
It is noteworthy to appreciate that statistically, the odds that the location of a near intersection will also satisfy geometry constraints diminishes as the number near intersections diminishes. And the number of intersections that can be considered “near” generally diminishes as the number of ambiguity fronts increase. Each added differential carrier phase measurement yields an added ambiguity front. Furthermore, while it is evident that three antennas is sufficient for a 3D solution, increasing the number of antennas also helps with ambiguity determinations since associated with each added baseline is another set of ambiguity fronts and another opportunity to insure that false intersections and geometry do not coincide.
Mathematically the DCPA equation provides a means to measure both the nearness of ambiguity front intersections and the degree to which these intersections satisfy geometry constraints. Its solution insures that both factors are taken into account. And since all independent baselines are simultaneously incorporated into the DCPA equation, all available information is used consistently and to its fullest extent.
One method to solve the DCPA equation for both the ambiguities {right arrow over (N)} and the angles Ψ,θ, and φ is to minimize a cost function that effectively characterizes the degree to which the ambiguity fronts intersect one another and the degree to which they lie on the constraining geometry. Usually, this involves a search of potential candidates of the ambiguity vector {right arrow over (N)} followed by a least-squares solution of the DCPA equation for each candidate. In the least-squares solution, the angles Ψ,θ, and φ are determined that minimize the cost function C where
C=E^{T}QE
Here, E is defined as the error vector associated with the solution of the DCPA equation. That is:
E={right arrow over (φ)}−[W _{d} ∥T _{d}(Ψ,θ,φ)]{right arrow over (V)}+{right arrow over (N)}.
The matrix Q is a weighting matrix that allows measurements to be weighted based on factors such as the noise levels that are expected within the single- or double-difference phase measurements. Noisy measurements are given less weight than non-noisy measurements. In practice, this noise is often a function of satellite elevation or signal-to-noise ratios.
The DCPA equation is nonlinear in Ψ,θ, and φ. Consequently a least-squares solution typically requires that the equation first be linearized about a nominal point and then solved by successive iterations involving new nominal points and new linearizations about the new nominal points.
The set of ambiguities that results in a global minimization of the cost function C is chosen as the correct set of ambiguities. That is, the set of all candidate ambiguity vectors {right arrow over (N)} are searched and Ψ,θ, and φ are determined that minimize C for each candidate {right arrow over (N)}. The candidate that results in the lowest value for C is taken as the correct candidate.
Turning now to
Both
It will also be appreciated that the process for searching over ambiguity values as depicted in
Turning now to
Process block 172 depicts the solution of the integer ambiguities, was described in greater detail in
The system progresses to process block 173, once integer ambiguities are determined, Ψ,θ, and φ are computed by solving the DCPA equation while using the previously determined ambiguities. If only one vector pair is utilized, only two of the three angles Ψ,θ, and φ can be computed. Solution for Ψ,θ, and φ is relatively straight forward and in one embodiment involves a standard least-squares method for simultaneously solving a set of linear equations as well as standard techniques from calculus for linearizing sets of nonlinear equations. In another exemplary embodiment, a Kalman filter may be employed as an alternative to the least-squares method; the advantage being that a Kalman filter can produce a solution that optimally utilizes knowledge of both measurement noise statistics and anticipated dynamics (e.g., maximum angular accelerations) of the attitude device.
Continuing with
It will be evident that there exist numerous numerical methodologies in the art for implementation of mathematical functions, in particular as referenced here, linearizations, least squares approximations, filters, Kalman filters, taking maximums, and summations. While many possible implementations exist, a particular method of implementation as employed to illustrate the exemplary embodiments should not be considered limiting.
The system and methodology described in the numerous embodiments hereinbefore provides a system and methods of attitude determination that is effective and completely exploits geometry constraints of the antennas attached to a rigid body, and does so with measurements from all antennas processed simultaneously and optimally. This occurs both during the solution of the ambiguities and during normal operation of the attitude device. In addition, the disclosed invention may be embodied in the form of computer-implemented processes and apparatuses for practicing those processes. The present invention can also be embodied in the form of computer program code containing instructions embodied in tangible media, such as floppy diskettes, CD-ROMs, hard drives, or any other computer-readable storage medium, wherein, when the computer program code is loaded into and executed by a computer, the computer becomes an apparatus for practicing the invention. The present invention can also be embodied in the form of computer program code, for example, whether stored in a storage medium, loaded into and/or executed by a computer, or as data signal transmitted whether a modulated carrier wave or not, over some transmission medium, such as over electrical wiring or cabling, through fiber optics, or via electromagnetic radiation, wherein, when the computer program code is loaded into and executed by a computer, the computer becomes an apparatus for practicing the invention. When implemented on a general-purpose microprocessor, the computer program code segments configure the microprocessor to create specific logic circuits.
It will be appreciated that the use of “first” and “second” or other similar nomenclature for denoting similar items is not intended to specify or imply any particular order unless otherwise specifically stated. Likewise the use of “a” or “an” or other similar nomenclature is intended to mean “one or more” unless otherwise specifically stated.
While the invention has been described with reference to an exemplary embodiment thereof, it will be understood by those skilled in the art that the present disclosure is not limited to such exemplary embodiments and that various changes may be made and equivalents may be substituted for elements thereof without departing from the scope of the invention. In addition, a variety of modifications, enhancements, and/or variations may be made to adapt a particular situation or material to the teachings of the invention without departing from the essential spirit or scope thereof. Therefore, it is intended that the invention not be limited to the particular embodiment disclosed as the best mode contemplated for carrying out this invention, but that the invention will include all embodiments falling within the scope of the appended claims.
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U.S. Classification | 342/357.36 |
International Classification | G01S19/53, G01S5/14 |
Cooperative Classification | G01S19/53 |
European Classification | G01S19/53 |
Date | Code | Event | Description |
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Oct 4, 2005 | AS | Assignment | Owner name: CSI WIRELESS, INC., CANADA Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:WHITEHEAD, MICHAEL L.;DAVIS, CARY;SCOTT, DALE R.;REEL/FRAME:017074/0078;SIGNING DATES FROM 20050913 TO 20050919 |
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