|Publication number||US7415367 B2|
|Application number||US 10/850,528|
|Publication date||Aug 19, 2008|
|Filing date||May 20, 2004|
|Priority date||May 20, 2003|
|Also published as||US7788050, US20040245995, US20080319689|
|Publication number||10850528, 850528, US 7415367 B2, US 7415367B2, US-B2-7415367, US7415367 B2, US7415367B2|
|Inventors||Thomas Holtzman Williams|
|Original Assignee||Arcom Digital, Llc|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (28), Non-Patent Citations (10), Referenced by (17), Classifications (8), Legal Events (4)|
|External Links: USPTO, USPTO Assignment, Espacenet|
This application is a continuation of U.S. provisional application No. 60/472,379 filed on May 20, 2003 titled System and Method to Locate Common Path Distortion of Cable Systems.
Two-way hybrid fiber coax (HFC) cable systems typically provide two-way communications for end users (typically homes or businesses) using both coaxial cable and fiber optic cable. A headend is a collection point for downstream signals and a termination point for upstream signals. “Downstream” or “forward” means signals traveling away from the headend and “upstream” or “reverse” means signals traveling toward the headend. The coaxial portion of cable networks uses a tree-and-branch architecture to split downstream signals and combine upstream signals. On the coaxial portion of the cable plant, downstream signals are sent from a headend to an end user in a downstream frequency band, which may be 54 to 860 MHz. The composite downstream signal is typically comprised of analog television signals in the lower frequencies, such as 54 to 550 MHz, and digital television signals and cable modem traffic in the upper frequency band, such as 550 to 860 MHz. Upstream signals travel from the end users to the headend in the 5 to 42 MHz upstream frequency band over the same coaxial cable that is used for downstream communications. The fiber portion of the plant is typically nearer to the headend and transports signals a long distance to a cluster of subscribers. The point at which the downstream fiber optic (light) signals are converted to downstream electrical signals for transmission over coaxial cable is called a fiber node. The upstream electrical signals are also converted into fiber optic signals at the fiber node for transmission back to the headend. In larger plants there may be additional signal distribution/collection points called “hubs”. In the United States the downstream is typically divided into 6 MHz channels that usually contain analog NTSC carriers or digital carriers. Normally, upstream channel spacing is not uniform.
Common path distortion (CPD) is an upstream impairment that is created on the coaxial portion of HFC cable systems. CPD is caused by downstream signals mixing together in non-linear elements to create an upstream interference that is comprised of distortion or inter-modulation products. CPD is typically produced by diodes that are formed by metallic corrosion in network elements such as taps, amplifiers, splitters, power inserters, and connectors. Finding the network element where the distortion is created is a difficult problem for cable technicians, because the act of touching or opening a network element frequently corrects the CPD problem, albeit temporarily.
With a large number of analog television channels (such as NTSC) on the downstream path, the upstream spectral plot caused by CPD has an appearance on a spectrum analyzer of three beats every 6 MHz across the return band. In the United States, with a standard frequency plan, second order distortion beats are centered every integer multiple of 6 MHz, and third order distortion beats are located every 1.25 MHz above and below the second order beats. If there are two radio frequency carriers at fa and fb, second order beats can be created by mixing products such as 2*fa, or 2*fb, or fa−fb, or fb−fa. If you have three carriers, such as fa, fb, and fc, third order beats can be created from many mixing products such as 3*fa, 3*fb, 3*fc, fa+fb+bf, 2fa−fb, 2fb−fc, 2fc−fa, etc. The distortion products at the 6 MHz increments are second order distortion products because television channel spacing in the United States is 6 MHz. The third order distortion products at plus and minus 1.25 MHz from the second order beats are offset because video carrier frequencies, such as channel 2 at 55.25 MHz and channel 3 at 61.25 MHz, are not integer multiples of 6 MHz in a standard frequency plan.
While CPD has been observed on the upstream cable plant, mixing from CPD products also fall into the downstream frequency spectrum, where a visual impairment will be created that is similar to CSO (common second order) or CTB (composite triple beat), which are well-known downstream impairments. Thus, customer complaints about excessive downstream CTB may, in fact, be partially downstream CPD distortion products. Thus there is a need to find and fix sources of CPD.
The prior art method of finding CPD is to disconnect upstream network elements one at a time until the CPD goes away. This is a trial and error process, which is slow and prone to error because of the aforementioned problem of temporarily fixing CPD when the defective element is disturbed. Disconnecting network elements also disrupts services.
A new method in use by Optus in Australia ranges a distance to a CPD source using custom-designed special-purpose test equipment. This method is described by Australian patent application TW474071. Their system is comprised of PC-based test equipment, which injects test signals into vacant bandwidth on the downstream plant. On many cable systems vacant bandwidth for testing does not exist.
Interference with cable entertainment signals, voice carriers and data traffic for test is generally unacceptable.
This invention discloses a better method by determining a time delay associated with a defective CPD-creating element by using signals that are already being transported on the cable system. The time delay may be used to compute a round-trip distance using the known velocity of propagation. Knowing a distance to the CPD-creating element allows the defective device to be identified from a network map that shows distances.
This invention also discloses an improved injected test signal method that uses standard off-the-shelf test equipment.
This invention is a system to range a distance to a source of CPD on a two-way cable system utilizing signals that are normally carried on the downstream signal path. The system is comprised of a local CPD source that generates a local distortion signal from a downstream signal, and a source of CPD that mixes the downstream signal to create an upstream actual distortion signal. A cross-correlator performs a cross-correlation between the local distortion signal and the upstream actual distortion signal to create a cross-correlation plot. A round-trip time to the source of CPD is determined from the cross-correlation plot, and the distance is determined from the round-trip time.
Other network elements, including a two-way amplifier 326 and taps 328, 330, and 332, are without defect and do not create an upstream CPD distortion signal from the downstream signal components.
The downstream signal 368 is sampled through a coupled port of the forward test point directional coupler 310, through a band pass filter/tilt network 334 and through an amplifier 336, to create a filtered downstream signal 311. The filtered downstream signal 311 is connected to a local CPD source 338. The band pass filter/tilt network 334 preferably passes only the digital signals, which are more noise-like and random, and thus better suited for use as test signals than the analog television carriers. The analog television carriers have strong periodic horizontal sync energy. In the local CPD source 338, a non-linear element, such as a Schottky diode 344, mixes the filtered downstream signal 368 to make a local distortion signal 342. The local distortion signal 342 is correlated to the energy in the actual distortion signal 202 that is created by digital carriers in the source of CPD 324. A high port of a diplex filter 348 is connected to the amplifier 336. A common port of the diplex filter 348 is connected to the diode 344 through a bypass capacitor 343. An inductor 346 holds the diode 344 at 0 volts DC so a clipping point will be repeatable. A resistor 340 provides an improved match for the diplex filter 348. A low port of diplex filter 348 removes the distortion products above 42 MHz. An amplifier 350 boosts the level of the local distortion signal 342 before it is captured on a digital data acquisition unit 354.
A sample of the actual distortion signal 202 is captured from the coupled port of the upstream test point directional coupler 314 and is amplified by an amplifier 352. The digital data acquisition unit 354 simultaneously captures an amplified sample of the actual distortion signal 202 on channel 1 and the local distortion signal 342 on channel 2. Both traces are downloaded over a cable 356 to a personal computer (PC) 358 where they are processed together to find a time delay between the actual distortion signal 202 and the local distortion signal 342. The PC 358, running software, acts as a cross-correlator 372. The cable 356 may be a general-purpose interface bus (GPIB), serial, parallel, or universal serial bus (USB) depending on the interface method provided by the data acquisition unit 354. The round-trip time delay to and from the source of CPD 324 can be established as the time of an energy peak in a cross-correlation plot 360. The cross-correlation plot 360 on the PC shows a time difference 362 required for downstream energy to travel to the source of CPD 324 and to come back to amplifier housing 302. The distance to the source of CPD 324 can be calculated from the round-trip time for a signal to travel to the source of CPD 324 and return, taking into account the velocity of propagation of the cable. This distance calculation from time delay, which is also used in radar and time domain reflectometers, is well known in the art.
The band pass filter/tilt network 334 may be used for cross-correlation signal improvement. Digital traffic is better suited for cross-correlation measurements than analog signals, which are not as random. It is advantageous to include as many digital channels as are available. Since tilt of the downstream signal at the CPD source will not be known in advance, the tilt may optionally be adjusted to produce the strongest cross-correlation peak with the lowest uncorrelated noise. The gain of the amplifier 336 may also be adjustable to improve the quality of the cross-correlation signal. Likewise, it may be desirable to reverse the polarity of the diode 344, since a polarity of the CPD-creating junction diode is not known in advance. That is, either an anode or a cathode may be connected to ground.
The digital acquisition unit captures signals by performing an A-D (analog-to-digital) conversion and storing the signals in memory for subsequent downloading. Both signals may be considered to be arrays of numbers. The processing between the captured local distortion signal 342 and the captured actual distortion signal 202 can be done with a cross-correlation process, which is well known in the art. A software package called Matlab®, which is available from Math Works® can perform the cross-correlation function. “C Language Algorithms for Digital Signal Processing” by Embree and Kimble is a source for code that can perform the cross-correlation function. It is an advantage to cross-correlate two large arrays of samples, since it will produce the lowest background noise relative to a cross-correlation peak. The array size may vary from a few hundred to several thousand samples. A sampling rate of 100 Megasamples per second or greater is recommended for the digital acquisition unit 354, which may be a digital oscilloscope, a data acquisition card for a PC, or a module from suppliers such as Link Instruments, Pico, or National Instruments. Triggering of the digital acquisition unit 354 may be random or tied to an event such as video horizontal sync or the power line frequency.
This testing method has the advantage over prior art systems of using downstream signals, which are already on the downstream plant, as test signals. On many cable systems vacant bandwidth for testing simply does not exist.
Note that the cross-correlation in the time domain function can also be accomplished by signal processing in the frequency domain by a multiplication operation, as is well known in the art. Depending on the skill of the technician, it may be an advantage to write a computer program which performs the downloading of data from the data acquisition unit 354 and the cross-correlation automatically, as well as automatically making adjustments to the gain of the amplifier 336 and the tilt of the band pass filter/tilt network 334. Averaging can be used to reduce the effects of noise or interfering signals in the cross-correlation plot 360.
Note that the diode 344 will produce second, third, fourth and higher orders of distortion. Other devices, such as field effect transistors will produce large amounts of second order distortion. If two identical diodes are connected in parallel anode-to-cathode the even order distortion products can be cancelled. Thus, the local CPD source 338 may be modified to enhance a desired order of mixing.
To summarize, the local CPD source 338 is connected to the sample of the downstream signal 368, and used to create the local distortion signal 342. The local distortion signal 342 is stored on one channel of the digital acquisition unit 354. At the same time, a sample of the actual distortion signal 202 from the defective CPD-producing element is captured on another channel of the digital acquisition unit 354. The two traces are processed by a cross-correlator 372. The peak on the cross-correlation plot 360 shows the number of microseconds of delay between the actual distortion signal 202 and local distortion signal 342. The delay can be used to range the distance between the amplifier housing 302 and the source of CPD 324. Multiple sources of CPD can be identified by this test method.
The test can be performed at any point in the network, such as a hub site, a headend, or a node, a main branch (trunk line), a secondary branch (feeder line), a tap location, or even the side of a house, if the house is the source of CPD. Likewise, any defective component creating an actual distortion signal 202 can be ranged and identified by this method.
Since distortion creation problems do not typically occur in the middle of cable spans, the time delay can be used to find the most probable defective component. For example, a location 364 in the plant has the same time delay as the source of CPD 324, but is probably not a CPD source because it is in the middle of a cable span.
The embodiment of
While being much simpler than the embodiment of
While some cable systems do not have any available vacant bandwidth for testing, other cable systems do. Another method to find the distance to a CPD source is to use a downstream frequency band and an equal bandwidth of upstream spectrum. The downstream frequency band should ideally be vacant to avoid interference with cable signals, but this method works even if the frequency band is occupied. This improved method uses an off-the-shelf network analyzer instead of custom-build hardware and software used by prior art methods.
Two signals can be put on the downstream signal path, one a fixed CW signal 436 and the other an up-converted swept signal 434. A mixing action of the fixed CW signal 436 with a swept signal 428 converts the swept signal 428 into the up-converted swept signal 434 in the downstream frequency band. The source of CPD mixes the up-converted swept signal 434 with the fixed CW signal 436 to create an upstream swept signal 432. The use of a conventional off-the-shelf network analyzer gives a complex frequency response associated with the returned upstream signal. The complex frequency response can be converted into the time domain via an inverse fast Fourier transform (IFFT). The IFFT option for the network analyzer is also called a “time domain option”. The temporal plot of the IFFT shows a round-trip delay time to the source of the CPD. Some network analyzers, such as an Agilent® 8753 can be purchased with the optional IFFT function. For network analyzers that do not have an IFFT option, it is possible to import the complex frequency response data into a computer and perform the IFFT with PC software. “C Language Algorithms for Digital Signal Processing” by Embree and Kimble is also a source for code that can perform the IFFT transform.
The frequencies illustrated in this example illustrate second order mixing, producing a difference frequency signal. It is also possible to choose frequencies that produce a third or other order mixing. An additional CW signal can be inserted to cause third order mixing. Note that when there is large delay time, the sweep rate of the network analyzer must be slowed down to compensate for signal delay.
Also observe that if a larger test bandwidth is available, the distance to the CPD source can be ranged more accurately. Ranging time accuracy is proportional to the inverse of the swept bandwidth. If there are other desired or undesired signal sources in the 5-30 MHz band they will cause interference with the upstream swept signal 432, but the network analyzer can be adjusted to minimize the interference. Averaging on the network analyzer can be used to minimize the interference.
The essential idea of the block diagram 400 of
As mentioned above, because a cable network typically has a tree and branch construction, there may be multiple possible locations on the network that correspond to the calculated CPD distance. However, it is exceedingly unlikely that CPD will be created in the middle of a piece of cable. Therefore, the distances associated with connectors, actives, and passives will be considered primary suspect locations.
If two CW carriers are inserted on a downstream cable plant, and they are mixed by second order mixing at a source of CPD, a resulting upstream CW signal will be created and propagate upstream. Delay can be determined from frequency response as a change in phase with respect to the change frequency. That is:
where phi is the phase in radians and omega is the frequency in radians per second. Thus, one only needs to tune one of the two CW carriers and observe a phase change with respect to frequency to determine the distance to a source of CPD.
The purpose of a first mixer 618 is to produce a mixing CW signal 622, which varies between 5 and 20 MHz. The frequency of the mixing CW signal 622 is the frequency difference between the tunable CW signal 636 and the fixed CW signal 634. A LO port of the first mixer 618 is connected to an output of the splitter 608 and an IF port of the first mixer 618 is connected to the splitter 606 through an attenuator 620. The attenuator 620 reduces the signal from the tunable signal generator 604 to approximately −10 dBm. The optimal LO level of the first mixer 618 and the second mixer 632 is assumed to be about +7 dBm. The mixing CW signal 622 passes through a low pass filter 624, which removes undesired mixing products and LO bleed-through. The output of the low pass filter 624 is connected to an amplifier 626 which boosts the LO drive level to the second mixer 632 to about +7 dBmv. The IF output of the second mixer 632 connects to a low pass filter 628, which may have a low corner frequency such as 10 kHz. The output of the low pass filter 628 is connected to a DC voltage display unit 630. The low pass filter passes the DC voltage while eliminating most noise.
Assuming that CPD is present, the output of the second mixer 632 will be a voltage that is a steady DC level while the tunable signal generator 604 is not being tuned, and will produce a sine wave voltage, centered about zero volts while the tunable signal generator 604 is being tuned. The output voltage can be displayed on a DC voltmeter, which deflects positive and negative relative to zero volts. Likewise, the voltage can be displayed on an oscilloscope, bar-graph or any other voltage indicating instrument.
The round-trip delay time associated with the round-trip distance to a source of CPD is determined by tuning the tunable signal generator 604 to find the frequency difference between positive-going voltage nulls, or two adjacent voltage peaks, on the DC voltage display unit 630. The reciprocal of the frequency is the unknown delay. For example, if the frequency difference between nulls is 100 kHz, the round-trip delay is 10 microseconds. For increased frequency accuracy, an operator may increase the number of positive-going voltage nulls and divide the frequency by the number of nulls used.
This method has an advantage of being conceptually simple and easy to operate, but if there are multiple large sources of CPD, the voltage deflection will not be a simple sinusoid, but move through a complicated periodic pattern, making distance ranging difficult
A tunable signal generator 704 produces a tunable sine wave signal 736, on a port labeled 0 deg, and a tunable cosine wave signal 738, on a port labeled 90 deg. Numerically controlled oscillators (NCOs) are one possible way to produce tunable CW outputs with both sine and cosine waves. Hilbert transformers are another way. A directional coupler 720 splits the tunable sine wave signal 736. One leg of the directional coupler 720 is connected to an IF port of the up-converting mixer 708. The other leg of the directional coupler 720 is connected to a LO port of an in-phase mixer 722. The RF port of the in-phase mixer 722 is connected to one output of the splitter 724. The other output of the splitter 724 is connected to the RF port of a quadrature mixer 726. The tunable cosine wave signal 738, is connected to a LO port of the quadrature mixer 726. An in-phase low pass filter 728 is connected between the IF output of the in-phase mixer 722 and an I (in-phase) output line 732. An IF output of the quadrature mixer 726 is connected to an input of a quadrature low pass filter 730. The output of the quadrature low pass filter 730 is connected to a Q (quadrature) output line 734. The low pass filters 728 and 730 may have a low bandwidth for good noise rejection, provided that the frequency of the tunable signal generator 704 is changed slowly. For example, the bandwidth could be between 1 kHz and 10 kHz.
The I and Q output lines can be used in several ways. In an oscilloscope is put into an X-Y mode and the I output line 732 is connected to the X-channel and the Q output line 734 is connected to the Y-channel, and there is one source of CPD present, as the frequency of the tunable signal generator 704 is changed, the trace on the oscilloscope will trace out a circle. This is an example of a Lissajous pattern. A reciprocal of the frequency change required to make a complete circle is the round-trip delay associated with the CPD source.
Alternately, if the frequency of the tunable signal generator 704 is changed in small and uniform steps, and the I output line 732 voltages and the Q output line 734 voltages are recorded by an analog-to-digital converter at each step, the complex frequency response associated with the source of CPD is obtained. The complex frequency response can be supplied to an IFFT process that will return the impulse response. The impulse response will show the time delay associated with each of multiple CPD sources. A personal computer (PC) can control a programmable voltmeter that measures the I and Q voltages and change the frequency of the tunable signal generator 704. Equipment control is commonly done using GPIB. Another approach is to use an embedded microprocessor in place of the PC. Essentially, you have assembled a poor-man's network analyzer with the equipment in diagram
A simplification is to remove the quadrature channel components: the quadrature mixer 726, the quadrature low pass filter 730, the splitter 724, and the cosine port on the tunable signal generator 704. This can be done by switching the tunable sine wave output 736 of the tunable signal generator 704 between a sine and cosine wave, and taking two voltage measurements on the I output line 732 for each frequency step. A NCO, such as the Analog Devices AD9850BRS has an ability to accurately change phase by 90 degrees on command.
Another Sweep System
Another sweep system that can be used in place of the network analyzer is the Cable Scope® system sold by Holtzman Inc. This device uses a burst test signal to produce the complex frequency response and impulse response. The round-trip time delay to a CPD source can be measured on the impulse response. In particular, the Cable Scope can be used in a local test configuration with the HE2M reference signal transmitter replacing the RF transmit output port 404 on the network analyzer 402 and a TDS-1002 digital oscilloscope replacing the RF receive input port 426 on the network analyzer 402.
Summary Ramifications and Scope
Although the description above contains many specificities, these should not be construed as limiting the scope of the invention, but as merely providing illustrations of some of the presently preferred embodiments of the invention. For example,
1. One may use another circuit to produce second order mixing in the local CPD source 338. For example, field effect transistors (FETs) have a square-law characteristic that can be exploited to produce good second order mixing.
2. The downstream digital carrier(s) that are selected to be test signals may be multiple 6 MHz wide carriers. For example, if second order mixing is used, a carrier can mix with another carrier that is 12 MHz away and create noise in the return band at 12 MHz. In general, as the number of carriers is increased, the background noise in the correlation plot decreases and the correlation peak increases.
3. If a cable system, such as a private or hospital system, has not yet deployed digital carriers, one or more digital carriers can be inserted for CPD location.
4. A band-limited random noise source may also be inserted and used as a test signal for CPD location.
5. The system of the present invention may be used for other applications such as satellite, microwave, or telephony.
6. Averaging may be used to increase the accuracy of all measurements. Averaging is particularly useful in the presence of additive return noise.
|Cited Patent||Filing date||Publication date||Applicant||Title|
|US3774201 *||Dec 17, 1970||Nov 20, 1973||Raytheon Co||Time compression signal processor|
|US5073822||Nov 19, 1990||Dec 17, 1991||Tektronix, Inc.||In-service cable television measurements|
|US5461318||Jun 8, 1994||Oct 24, 1995||Borchert; Marshall B.||Apparatus and method for improving a time domain reflectometer|
|US5617137||May 30, 1995||Apr 1, 1997||Tektronix, Inc.||In-service measurement of composite triple beats in a cable television system|
|US5682100||Sep 6, 1995||Oct 28, 1997||Electric Power Research Institute Inc.||System and method for locating faults in electric power cables|
|US5990687||May 29, 1997||Nov 23, 1999||Williams; Thomas H.||Measuring shield breaks in coaxial cable by a sheath test current|
|US6140822||Nov 7, 1998||Oct 31, 2000||Williams; Thomas H.||System for signal path characterization with a reference signal using stepped-frequency increments|
|US6151559||Jun 21, 1997||Nov 21, 2000||Williams; Thomas H.||System and method for characterizing undesirable noise of a signal path within a selected frequency band|
|US6344749||Dec 6, 1997||Feb 5, 2002||Thomas H. Williams||Test system for measuring frequency response and dynamic range on cable plant|
|US6356555 *||Jul 19, 1996||Mar 12, 2002||Terayon Communications Systems, Inc.||Apparatus and method for digital data transmission using orthogonal codes|
|US6417942 *||Feb 3, 1999||Jul 9, 2002||Kabushiki Kaisha Toshiba||Optical communication system and method of controlling optical communication system|
|US6425132||Apr 6, 1998||Jul 23, 2002||Wavetek Corporation||Ingress testing of CATV system utilizing remote selection of CATV node|
|US6570394||Jan 16, 2001||May 27, 2003||Thomas H. Williams||Tests for non-linear distortion using digital signal processing|
|US6687632 *||Jan 22, 1999||Feb 3, 2004||Trilithic, Inc.||Testing of CATV systems|
|US7069163||Apr 23, 2003||Jun 27, 2006||Utah State University||Digital spread spectrum methods and apparatus for testing aircraft wiring|
|US20010051504 *||Mar 14, 2001||Dec 13, 2001||Tokuro Kubo||Activation method of communications apparatus with a non-linear distortion compensation device|
|US20020086641 *||Nov 16, 2001||Jul 4, 2002||Howard Daniel H.||Method and apparatus for detection and classification of impairments on an RF modulated network|
|US20020161542 *||Mar 16, 2001||Oct 31, 2002||Jones Keith R.||Method and apparatus for transmission line analysis|
|US20040039976||Apr 23, 2003||Feb 26, 2004||Jacob Gunther||Digital spread spectrum methods and apparatus for testing aircraft wiring|
|US20040073937||Sep 30, 2002||Apr 15, 2004||Williams Thomas H.||System and method to test network performance with impairments|
|US20040091055||Oct 30, 2003||May 13, 2004||Williams Thomas Holtzman||Digital transmission system using non-orthogonal matrices|
|US20060012376||Aug 4, 2005||Jan 19, 2006||University Of Utah||Method and apparatus for characterizing a signal path carrying an operational signal|
|EP0487306A2||Nov 19, 1991||May 27, 1992||Tektronix Inc.||In-service cable television measurements|
|JPS60176336A||Title not available|
|SU1132265A1||Title not available|
|WO1997020196A1||Dec 6, 1995||Jun 5, 1997||Bicc Public Limited Company||Device for interrogating an optical fibre network|
|WO2000057571A1||Mar 23, 2000||Sep 28, 2000||Cable & Wireless Optus Ltd.||Coaxial cable fault locator|
|WO2004070398A2||Feb 4, 2004||Aug 19, 2004||University Of Utah Research Foundation||Method and apparatus for characterizing a signal path carrying an operational signal|
|1||CPD Fault Locator, by Rod Eastment et al Source: www/scte.org.|
|2||Int'l Search Report, Oct. 2, 2006, PCT/US2006/006360, pp. 2-3, 5-6.|
|3||Lee, Edward A. & Messerschmitt, David G., Digital Communication, Second Edition, reference book, 1994, pp. 231-234, Kluwer Academic Publishers, Norwell, MA.|
|4||Patel, Bharat, Common Path Distortions Explained, article, Oct. 13, 1998, pp. 1-2, 5-9, 16-18, 22-23, 27-28, SCTE, http://chapters.scte.org/newengland/reference/CPD/CPD2.HTM.|
|5||Williams, Thomas H., et al., Results of Return Plant Testing, Symposium, Jun. 1997, pp. 142-165, 1997 NCTA Technical Papers.|
|6||Williams, Thomas Holtzman, Cable Scope(R) Instruction Manual, 1998-2003, pp. 1-10, 13-15, 20-22, 24-30, Holtzman Inc., Longmont, Co.|
|7||Williams, Thomas Holtzman, Proofing and Maintaining Upstream Cable Plant With Digital Signal Analysis Techniques, 49th ARFTG Conference Digest, Jun. 13, 1997, pp. 7-18.|
|8||Williams, Thomas Holtzman, Return Path Linear Distortion and Its Effect on Data Transmissions, Symposium, Jun. 2000, pp. 54-71, 2000 NCTA Technical Papers.|
|9||Written Opinion w/Claims, Oct. 2, 2006, PCT/US2006/006360, pp. 10-21.|
|10||Zhang, Yun Hong & Jennings, Len, DSP Applictions in Range Finding, article, Jan. 1, 2002, pp. 61-66, New Zeland, http://www.manukau.ac.nz/departments/e<SUB>-</SUB>e/research/2002/yz.pdf.|
|Citing Patent||Filing date||Publication date||Applicant||Title|
|US7584496||Jan 3, 2006||Sep 1, 2009||Arcom Digital, Llc||Method and apparatus for pinpointing common path distortion|
|US8458759 *||Jun 18, 2008||Jun 4, 2013||Arcom Digital, Llc||Method and apparatus for locating network impairments|
|US8756031 *||Jul 13, 2010||Jun 17, 2014||International Business Machines Corporation||Matched filter testing of data transmission cables|
|US8894297 *||Aug 17, 2012||Nov 25, 2014||Via Technologies, Inc.||Active optical cable with an additional power connector, and electronic device using the same|
|US8981991 *||Apr 30, 2010||Mar 17, 2015||Robert Bosch Gmbh||Mixer assembly and radar sensor for motor vehicles|
|US9160407||Jun 26, 2012||Oct 13, 2015||Trilithic, Inc.||Method for detecting leakage in digitally modulated systems|
|US9209863||Aug 9, 2013||Dec 8, 2015||Cable Television Laboratories, Inc.||Analysis of captured random data signals to measure linear and nonlinear distortions|
|US9225387||Feb 19, 2014||Dec 29, 2015||Cable Television Laboratories, Inc.||Analysis of captured signals to measure nonlinear distortion|
|US9414126||Mar 9, 2015||Aug 9, 2016||Arcom Digital, Llc||Passive time domain reflectometer for HFC network|
|US9590696||Jun 10, 2015||Mar 7, 2017||Cable Television Laboratories, Inc.||Analysis of captured random data signals to measure linear and nonlinear distortions|
|US20060248564 *||Jan 3, 2006||Nov 2, 2006||Zinevitch Victor M||Method and apparatus for pinpointing common path distortion|
|US20080320541 *||Jun 18, 2008||Dec 25, 2008||Zinevich Victor M||Method and apparatus for locating network impairments|
|US20090113511 *||Dec 14, 2007||Apr 30, 2009||Hoseo University Academic Cooperation Foundation||Distortion and noise canceling system for hfc networks|
|US20120016618 *||Jul 13, 2010||Jan 19, 2012||International Business Machines Corporation||Matched filter testing of data transmission cables|
|US20120086594 *||Apr 30, 2010||Apr 12, 2012||Robert Bosch Gmbh||Mixer assembly and radar sensor for motor vehicles|
|US20130129283 *||Aug 17, 2012||May 23, 2013||Via Technologies, Inc.||Active optical cable and electronic device using the same|
|WO2016065094A1||Oct 22, 2015||Apr 28, 2016||Arcom Digital, Llc||Detecting cpd in hfc network with ofdm signals|
|U.S. Classification||702/59, 725/107, 348/192, 348/E17.001|
|International Classification||G01R31/00, H04N17/00|
|Aug 21, 2006||AS||Assignment|
Owner name: ARCOM DIGITAL, LLC, NEW YORK
Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:WILLIAMS, THOMAS HOLTZMAN;REEL/FRAME:018152/0155
Effective date: 20060818
|Oct 14, 2008||CC||Certificate of correction|
|Feb 20, 2012||FPAY||Fee payment|
Year of fee payment: 4
|Feb 8, 2016||FPAY||Fee payment|
Year of fee payment: 8