Publication number | US7869493 B2 |

Publication type | Grant |

Application number | US 11/573,138 |

PCT number | PCT/SG2005/000265 |

Publication date | Jan 11, 2011 |

Filing date | Aug 3, 2005 |

Priority date | Aug 3, 2004 |

Fee status | Paid |

Also published as | CN101023590A, CN101023610A, CN101023610B, EP1774684A1, EP1774684A4, EP1774684B1, EP1779531A1, EP1779531A4, US8218694, US20080260070, US20090232261, WO2006014141A1, WO2006014142A1 |

Publication number | 11573138, 573138, PCT/2005/265, PCT/SG/2005/000265, PCT/SG/2005/00265, PCT/SG/5/000265, PCT/SG/5/00265, PCT/SG2005/000265, PCT/SG2005/00265, PCT/SG2005000265, PCT/SG200500265, PCT/SG5/000265, PCT/SG5/00265, PCT/SG5000265, PCT/SG500265, US 7869493 B2, US 7869493B2, US-B2-7869493, US7869493 B2, US7869493B2 |

Inventors | Chin Keong Ho, Yan Wu, Sumei Sun, Zhongding Lei |

Original Assignee | Agency For Science, Technology And Research |

Export Citation | BiBTeX, EndNote, RefMan |

Patent Citations (22), Non-Patent Citations (1), Classifications (13), Legal Events (4) | |

External Links: USPTO, USPTO Assignment, Espacenet | |

US 7869493 B2

Abstract

A method for detecting a signal received via a communication channel, the communication channel being affected by noise, is described, wherein the received signal is processed according to a filtering step (**202**), the filtering step comprises multiplication of at least one component of the received signal with a filter coefficient and the filter coefficient comprises a noise variance offset which corresponds to the variance of the noise.

Claims(3)

1. A method for detecting a signal received via a communication channel, the communication channel being affected by noise, wherein:

the received signal is grouped into a plurality of blocks and is processed according to a filtering step which corresponds to the multiplication of a block of the received signal with a filtering matrix, wherein the filtering matrix corresponds to a product of matrices, where one of the matrices is a channel coefficient matrix that comprises components which are terms of channel coefficients that specify the transmission characteristics of the chanel;

the filtering step comprises multiplication of at least one component of the received signal with a filter coefficient; and

the filter coefficient comprises a noise variance offset which corresponds to the variance of the noise;

wherein at least one of the components of the channel coefficient matrix is a term of a channel coefficient and the variance of the noise;

wherein at least one of the components of the channel coefficient matrix is the conjugate of a channel coefficient divided by the sum of the square of the absolute value of the channel coefficient and square of the noise variance.

2. A method according to claim 1 , wherein at least one of the components of the channel coefficient matrix is the inverse of a channel coefficient.

3. A method according to claim 1 , wherein the variance of the noise of the channel is determined.

Description

The invention relates to a method for detecting a signal, a detector and a computer program product.

In mobile communications, high user capacities and high data rates are desirable. To achieve this, mobile radio systems have to be highly spectral efficient. Using multicarrier modulation according to OFDM (orthogonal frequency division multiplexing) robust performance and high spectral efficiency can be achieved.

Before the OFDM modulation, a pre-transform can be carried out, resulting in a so-called PT-OFDM (pre-transform OFDM) system.

In [1] (and also in [2]), an iterative detection algorithm for a PT-OFDM system is described. This will be described in the following.

An iteration (corresponding to an iteration index i) of the iterative detection algorithm corresponds to three stages, a reconstruction step, a linear filtering step and a decision step.

In the ith reconstruction step, i.e. in the reconstruction step of the iteration corresponding to the iteration index i, the m_{i}th component of the received signal r (received signal vector) is estimated. This is done by using the previously detected symbol __{circumflex over (x)}__ _{i−1 }(i.e. the signal vector detected in the previous iteration). m_{i }corresponds to the frequency domain channel with the ith smallest amplitude. In the filtering step, the cross interference of the data is removed by a linear filter denoted by G. In the detection step, a tentative (hard or soft) decision (denoted by dec(.)) is made to generate the symbol detected in the ith iteration, __{circumflex over (x)}__ _{i}.

The algorithm is initialized with __r__ _{0}=__r__, __{tilde over (x)}__=__Gr__ _{0 }and __{circumflex over (x)}__ _{0}=dec(__{tilde over (x)}__ _{0}).

The ith iteration is given by:

* r *

where 0

In [1], the filter used in the iterative detection algorithm is based on the least squares criteria, also known as zero forcing (ZF) filter. Improvement is marginal even when a filter based on standard minimum mean squared error (MMSE) is used.

An object of the invention is to increase the performance of existing detecting methods.

The object is achieved by a method for detecting a signal, a detector and a computer program product with the features according to the independent claims.

A method for detecting a signal received via a communication channel is provided, wherein the communication channel is affected by noise, wherein the received signal is processed according to a filtering step, the filtering step comprises multiplication of at least one component of the received signal with a filter coefficient and the filter coefficient comprises a noise variance offset which corresponds to the variance of the noise.

Further, a detector and a computer program product according to the method for detecting a signal described above are provided.

**100** according to an embodiment of the invention.

**200** according to an embodiment of the invention.

Illustratively, a filter is used for reconstructing the received signal which has the noise variance of the channel as additional input and which processes the received signal in dependence of the magnitude of the variance of the noise that affects the channel. At least one filter coefficients of the filter is modified by an offset made up by the noise variance. This means that at least one filter coefficient is a term that comprises the noise variance as summand.

Especially in cases of high SNR (signal to noise ratio), using the invention, a performance gain in terms of BER (bit error rate) with respect to prior art methods can be achieved.

Embodiments of the invention arise form the dependent claims. Embodiments of the invention which are described in the context of the method for detecting a signal are analogously valid for the detector and the computer program product.

In one embodiment, the received signal is grouped into a plurality of blocks.

The processing of the received signal according to the filtering step may corresponds to the multiplication of a block of the received signal with a filtering matrix.

The filtering matrix may correspond to a product of matrices, wherein one of the matrices is a channel coefficient matrix that comprises components which are terms of channel coefficients that specify the transmission characteristics of the channel.

A channel coefficient is typically denoted by h and specifies the impulse responses of the channel, for example in the frequency domain.

In one embodiment, at least one of the components of the channel coefficient matrix is a term of a channel coefficient and the variance of the noise. In another embodiment, a plurality of the components of the channel coefficient matrix are terms of a channel coefficient and the variance of the noise.

For example, at least one of the components of the channel coefficient matrix is the conjugate of a channel coefficient divided by the sum of the square of the absolute value of the channel coefficient and the noise variance.

At least one of the components of the channel coefficient matrix can be the inverse of a channel coefficient.

In one embodiment, the variance of the noise of the channel is determined.

The invention can for example be used in communication systems according to WLAN 11a, WLAN 11g, WLAN 11n, Super 3G, HIPERLAN 2 and WIMAX (Worldwide Interoperability for Microwave Access) and B3G (beyond 3G).

**100** according to an embodiment of the invention.

The transmitter/receiver system **100** is formed according to a PT-OFDM (Pre-Transform Orthogonal Frequency Division Multiplexing) system. For simplicity it is assumed that M=2^{k}, e.g. M=32, and that M information symbols x_{m}, m=1, 2, . . . , M are transmitted at the same time in form of one OFDM symbol. For transmitting these information symbols, the vector of information symbols, __x__=[x_{1}, x_{2}, . . . , x_{m}]^{T}, in the following also called the original signal vector, is fed to a pre-transform unit **101**. The superscript T denotes the transpose operator.

The pre-transform unit **101** calculates a vector of modulation symbols __s__=[s_{1}, s_{2}, . . . , s_{M}]^{T }for the original signal vector according to

* s=W·x. *

The vector (or block) of modulation symbols __s__ generated by the pre-transform unit **101** is then passed to an IFFT (inverse fast Fourier transform) unit **102** which carries out an inverse fast Fourier transform on the block of modulation symbols.

The inverse fast Fourier transform is used in this embodiment as an efficient realization of an inverse Fourier transform. Other domain transformations can be used instead of the inverse fast Fourier transform, for example an inverse discrete sine transform or an inverse discrete cosine transform.

The vector generated by the IFFT unit **102** is then mapped from parallel to serial, i.e. to a sequence of signal values, by a P/S (parallel to serial) unit **103**. A cyclic prefix unit **104** inserts a cyclic prefix into the sequence of signal values to form a PT-OFDM symbol which is transmitted via a channel **105**.

The cyclic prefix that is inserted has a duration no shorter than the maximum channel delay spread. The channel **105** is assumed to be a quasi/static frequency selective Rayleigh fading channel corrupted by additive white Gaussian noise (AWGN).

The pre-transform unit **101**, the P/S unit **102** and the cyclic prefix unit **104** are part of a transmitter **106**.

The PT-OFDM symbol is received by a receiver **107**. A cyclic prefix removal unit **108** removes the cyclic prefix from the PT-OFDM symbol. The resulting sequence of signal values is mapped from parallel to serial by a S/P unit **109** and is domain transformed according to a fast Fourier transform by an FFT (fast Fourier transform) unit **110**. Analogously to the IFFT unit **102**, the FFT unit **110** can in other embodiments also be adapted to perform a discrete sine transform or a discrete cosine transform or another domain transformation.

The output vector of the FFT unit **110** is denoted by __r__=[r_{1}, r_{2}, . . . , r_{m}]^{T }and can be written as

* r=Γ·s+n=Γ·W·x+n *

where

The output vector __r__ of the FFT unit **110** is fed to a detection unit **111**. The detection unit **111** performs an iterative detection algorithm. An iteration (corresponding to an iteration index i) of the iterative detection algorithm corresponds to three stages, a reconstruction step, a linear filtering step and a decision step.

In the ith reconstruction step, i.e. in the reconstruction step of the iteration corresponding to the iteration index i, the m_{i}th component of the vector r is estimated. This is done by using the previously detected symbol __{circumflex over (x)}__ _{x−1 }(i.e. the signal vector detected in the previous iteration). m_{i }corresponds to the frequency domain channel with the ith smallest amplitude. In the filtering step, the cross interference of the data is removed by a linear filter denoted by G. In the detection step, a tentative (hard or soft) decision (denoted by dec(.)) is made to generate the symbol detected in the ith iteration, __{circumflex over (x)}__ _{i}. When the last iteration has been performed (e.g. after a given number of iterations, e.g. 4, has been performed) the detected symbols __{circumflex over (x)}__ _{i }are output by decision units **112**.

The algorithm is initialized with __r _{0} __=

The ith iteration is given by:

* r *

where

Under the assumption that the variance of the noise corrupting the channel **105** is known, the MMSE (minimum mean square error) filter described in the following can be used by the detection unit **111** to improve the performance of the transmitter/receiver system **100**.

Taking into account the MMSE criteria and assuming that previous detected symbols are correct for each reconstruction, the linear filter for the ith (i=1, 2, . . . , M) iteration can be derived:

and σ^{2 }is the noise variance. This __G__ is used in the filtering step of the reconstruction algorithm carried out by the detection unit **111** as described above.

For the initial iteration of the reconstruction algorithm, the MMSE filter with

β_{m} *=h* _{m}*/(|*h* _{m}|^{2}+σ^{2}), m=1*, . . . , M. *

is used.

When the matrix __W__ is chosen as unitary and has constant amplitude elements, even when the MMSE filter is used, the choice of m_{i }is unchanged (corresponding to the frequency domain channel with the ith smallest amplitude). That is, this choice still maximizes the worse post-filtered SNR at every detection step under the assumption that the previous detection is correct.

Simulations show that using this filter, the error floor can be reduced and superior performance can be achieved for high SNR. Note that this MMSE filter requires the knowledge that the noise variance is known at the receiver. However, simulations show that it is robust to noise variance errors.

In one embodiment, the reconstruction is extended as will be described with reference to

**200** according to an embodiment of the invention.

The receiver **200** may be used instead of the receiver **107** shown in **100**. The receiver **200** comprises a detection unit **201** and, corresponding to the decision units **112** of the receiver **107** shown in **206**. Analogously to the receiver **107**, the receiver **200** comprises other functional units, for example an FFT unit, which are not shown in

Analogously to the detection unit **111**, a vector __r__, e.g. the output vector of an FFT unit performing an FFT, is fed to the detection unit **201**.

A filtering unit **202** of the receiver **201** performs a filtering step of a reconstruction algorithm, e.g. the initial filtering step of the reconstruction algorithm described above. The result of the filtering step, denoted by __{tilde over (x)}__ _{0 }in accordance to the above description of the reconstruction algorithm is supplied to a first nonlinear detection unit **203**.

The receiver further comprises a second nonlinear detection algorithm unit **205**. The structure of the first nonlinear detection unit **203** and the second nonlinear detection unit **205** are described in the following with reference to

**300** according to an embodiment of the invention.

The nonlinear detection unit performs an ordered interference cancellation algorithm as will be described in the following.

The input vector of the non-linear detection unit **300** is a soft estimate of a transmitted signal (in case of the first non-linear detection unit, this is the output __{tilde over (x)}__ _{0 }of the filtering unit **202**). The input vector of the non-linear detection unit **300** is fed to an ordering unit **301**.

The ordering unit **301** performs an ordering step by obtaining the minimum Euclidean distance of the input to any point of the signal constellation. Then, the components of the input vector are ordered from largest to smallest (minimal) Euclidean distance and a hard decision is performed on the components of the input vector to form c_{1}, c_{2}, . . . , c_{M}.

c_{1}, c_{2}, . . . , c_{M }are fed to a cancellation unit **302** which performs the following algorithm:

For interference cancellation j=1, . . . , J,

(i) use {c_{k}}_{k≠j }to cancel from reconstructed received signal __r__ _{i }to obtain a soft estimate of c_{j }

(ii) perform hard decision on the soft estimate and update the newly detected c_{j }

(iii) increment j and continue with (i)

J is the number of cancellation steps and is for example chosen equal to M.

Illustratively, the interference cancellation algorithm uses the “best” components of the estimate, in the sense that they have minimal Euclidean distance to the signal constellation to improve the “worse” components, which have a higher Euclidean distance to the signal constellation.

The output of the first cancellation unit **302** is fed to the reconstruction unit **204**. The reconstruction unit **204** performs the reconstruction step and the filtering step for the ith iteration (where i=1, 2, . . . ) according to the reconstruction algorithm described above.

The result of each iteration performed by the reconstruction unit **204** is fed to the second non-linear detection unit **205**. The output of the second non-linear detection unit **205** is fed back to the reconstruction unit **204** for the next iteration to be performed except for the last iteration, when the output is supplied to the decision units **206** which generate the output of the receiver **200**.

The receiver **200** can also be used with a pre-transform (according to a matrix __W__) according to prior art and with a filter (according to a matrix __G__) according to prior art. This means that the idea of ordering the signal values according to a distance measure and using the signal values which are best (in terms of smallest distance) to cancel the interference from the other signal values is independent from using a pre-transformation matrix and from using a filter which is dependent on the variance of the noise of the channel used for data transmission.

In the above, the following documents are cited:

- [1] Receiver Having a Signal Reconstructing Section for Noise Reduction, System and Method Thereof, International Application Number: PCT/SG02/00194
- [2] Z. Lei, Y. Wu, C. K. Ho, S. Sun, P. He, and Y. Li, “Iterative detection for Walsh-Hadamard Transformed OFDM”, in Proc. 57
^{th }IEEE Vehicular Technology Conf., Jeju, Korea, April 2003, pp. 637-640

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Classifications

U.S. Classification | 375/229, 375/232, 375/240.26, 375/240.29 |

International Classification | H03H7/40, H03K5/159, H03H7/30 |

Cooperative Classification | H04L27/2634, H04L27/2602, H04L27/2649 |

European Classification | H04L27/26M1, H04L27/26M5A, H04L27/26M2G |

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Dec 3, 2008 | AS | Assignment | Owner name: AGENCY FOR SCIENCE, TECHNOLOGY AND RESEARCH, SINGA Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:HO, CHIN KEONG;WU, YAN;SUN, SUMEI;AND OTHERS;REEL/FRAME:021922/0122;SIGNING DATES FROM 20070606 TO 20070613 Owner name: AGENCY FOR SCIENCE, TECHNOLOGY AND RESEARCH, SINGA Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:HO, CHIN KEONG;WU, YAN;SUN, SUMEI;AND OTHERS;SIGNING DATES FROM 20070606 TO 20070613;REEL/FRAME:021922/0122 |

Mar 1, 2011 | CC | Certificate of correction | |

Aug 5, 2014 | FPAY | Fee payment | Year of fee payment: 4 |

Aug 5, 2014 | SULP | Surcharge for late payment |

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