|Publication number||US8048732 B2|
|Application number||US 12/701,896|
|Publication date||Nov 1, 2011|
|Filing date||Feb 8, 2010|
|Priority date||Jul 7, 2004|
|Also published as||US7683433, US20070069306, US20100134182|
|Publication number||12701896, 701896, US 8048732 B2, US 8048732B2, US-B2-8048732, US8048732 B2, US8048732B2|
|Inventors||Ashok Kumar Kapoor, Robert Strain, Reuven Marko|
|Original Assignee||Semi Solutions, Llc|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (88), Non-Patent Citations (17), Referenced by (8), Classifications (18), Legal Events (1)|
|External Links: USPTO, USPTO Assignment, Espacenet|
This application is a divisional of U.S. patent application Ser. No. 11/533,332, filed Sep. 19, 2006, now U.S. Pat. No. 7,683,433, which is a continuation-in-part of U.S. patent application Ser. No. 11/029,542, filed Jan. 4, 2005, now U.S. Pat. No. 7,224,205, and which claims priority from U.S. provisional patent application Ser. No. 60/717,769, filed Sep. 19, 2005, each of which is incorporated herein in its entirety by this reference thereto. U.S. patent application Ser. No. 11/533,332 further claims priority from U.S. provisional patent application Ser. Nos. 60/601,979, filed Aug. 17, 2004, and 60/585,582, filed Jul. 7, 2004, each of which is incorporated herein in its entirety by this reference thereto.
1. Technical Field
The invention relates to MOS transistors. More specifically, the invention relates to the improvement of drive-strength and leakage of deep submicron MOS transistors.
2. Discussion of the Prior Art
Users of conventional complementary metal-oxide semiconductor (CMOS) technology currently face some difficult choices as the minimum feature size of such devices shrinks to below 100 nanometers and power supply voltage is reduced to less than 1.0V. A typical layout of a 0.18 micron transistor 100 is shown in
While power supply voltage is decreased, the threshold voltage of NMOS transistors has stayed between 0.45V and 0.35V. The relationship between the NMOS threshold voltage Vth and CMOS power supply VDD is known to be very critical. The threshold voltage determines the leakage current Ioff of the transistor when it is in its OFF state. As the threshold voltage is driven lower, the leakage current increases.
The drain current of the transistor is a direct function of the overdrive of the transistors, measured as the difference between power supply VDD and threshold voltage Vth. The drain current of the transistor determines the time required to charge the load capacitance from ground to the level of power supply VDD, or vice versa. This overdrive voltage has decreased constantly as the power supply decreased from 3.3V to 1.0V, while threshold voltage decreased only from 0.45V to 0.35V. For 0.1 micron technology, the threshold voltage of the transistors is scaled below 0.35V at the expense of a very high OFF stage leakage current IOFF, which ranges between 1 nA to 100 nA for a transistor having a width of 1 miron. For a transistor with gate width of 10 microns, the OFF current increases to ten times the value stated above, i.e. from 10 nA to 1000 nA. For CMOS technology having a 0.1-micron minimum feature size, a typical VLSI chip is expected to contain over 100 million gates. Given a leakage of every gate of 1 microamperes, this results in a whopping 100 amperes of leakage current.
A scheme for dynamically controlling the transistor threshold voltage has been proposed by Takamiya et al. in High Performance Electrically Induced Body Dynamic Threshold SOI MOSFET (EIB-DTMOS) with Large Body Effect and Low Threshold Voltage IEDM Technical Digest 1998. Takimiya et al. suggest a scheme that shorts the gate and the substrate of the transistors, thereby causing the substrate voltage of the transistor to increase as the gate voltage is increased for an n-channel MOS (NMOS) transistor. This scheme is proposed for NMOS transistors fabricated on silicon-on-insulator (SOI) substrates, where the transistor substrate is totally isolated. This scheme manipulates the threshold voltage by changing the bias of the substrate or well in the positive direction for a NMOS transistor, along with a positive signal at the gate. As the substrate or well-to-source voltage becomes positive, the depletion layer width is reduced resulting in lower threshold voltage for the transistor, thereby increasing the current from the transistor. In the native form, Takimiya et al. is applicable only for circuits using a power supply voltage of less than 0.6V because this scheme turns on the substrate-to-source diode and the leakage from this diode must be limited or one would trade one type of leakage for another, i.e. from drain-to-source leakage to substrate-to-source leakage. Another approach is discussed in U.S. Pat. No. 6,521,948 by Ebina trying to solve is the accumulation of holes, created by impact ionization, in the floating body region of a semiconductor-on-insulator (SOI) transistor. The accumulated holes cause a relatively uncontrolled decrease in threshold voltage. Therefore, Ebina places the body into a slight, presumably controlled, forward bias conditions with respect to the source by connecting a reverse biased diode. Specifically, Ebina concentrates on controlling the current in the ON state, in particular to avoid its variable and uncontrolled increase. The use of a backward biased diode is deficient in several ways. Firstly, the reverse current through the diode varies over orders of magnitude and is highly sensitive to temperature. Secondly, the expanded polysilicon gate region creates a depletion region in the SOI substrate, and more explicitly in fully depleted SOI, which effectively cuts off the end of the gate from the source or the drain region during the ON state of the transistor. Secondly, while Ebina deals effectively with voltage ranges of 2 volts and above, it fails to provide a solution for transistor operating in lower voltages as common in modern designs.
Douseki in U.S. Pat. No. 5,821,769 describes a method for the control of the threshold voltage of an MOS transistor by connecting a MOS transistor between the gate and the substrate to control the threshold voltage. Douseki requires the addition of another transistor for every transistor whose threshold voltage is dynamically controlled. The adjusted threshold voltage is fixed by the power supply voltage and the threshold voltage of the additional transistor. The area penalty is fairly large for this approach and it requires additional process steps.
There is a therefore a need in the art for a technology which can reduce the leakage of MOS transistors without adversely affecting the drive current or the drain current under saturation conditions, which are defined as drain-source voltage and gate-source voltage equal to the power supply voltage (VDS=VGS=VDD). It would be further advantageous if the solution addressed low voltage operation in the range of 2V and below.
An apparatus and method of manufacture for metal-oxide semiconductor (MOS) transistors is disclosed. Devices in accordance with the invention are operable at voltages below 2V. The devices are area efficient, have improved drive strength, and have reduced leakage current. The inventive devices use a dynamic threshold voltage control scheme that is implemented without changing the existing MOS technology process. This scheme controls the threshold voltage of each transistor. In the OFF state, the magnitude of the threshold voltage of the transistor is increase, keeping the transistor leakage to a minimum. In the ON state, the magnitude of the threshold voltage is decreased, resulting in increased drive strength. The invention is particularly useful in MOS technology for both bulk and silicon on insulator (SOI) CMOS. The use of reverse biasing of the well, in conjunction with the above construct to further decrease leakage in a MOS transistor, is also shown.
The invention comprises the addition of a circuit to a MOS transistor, for example an NMOS transistor, that results in an increase in drive current while the transistor is in an ON state, and a reduction in leakage current while the transistor is in the OFF state. Specifically, this is achieved by implementing a control circuit between the gate and the substrate or well of the transistor. The control circuit may be comprised of linear and/or non-linear passive components and can be as simple as a resistor, a capacitor, or include one or more diodes, in a plurality of combinations suitable for leakage current reduction. Specifically, the circuit forces a high threshold voltage VTH in the OFF state of the NMOS transistor and a low VTH in the ON state of the NMOS transistor. A person skilled in the art would note that such a control circuit would work equally well with a PMOS type transistor. A detailed description of the disclosed invention follows.
The diodes are fabricated by a variety of techniques, as detailed below. One such type of diode is a diffused diode. These diodes are conventional diodes that are fabricated by diffusing n-type and p-type layers in a completed isolated structure. The voltage across the diodes is controlled by adjusting the doping profiles in silicon and programming the area, thereby controlling the voltage drop across the diode.
The diodes are formed differently for NMOS and PMOS transistors. The NMOS transistors are formed in a region isolated from the p-type substrate or well by a single or multiple deep N type implant. This isolation is achieved by existing triple well CMOS technology, a term known to those skilled in the art. This isolation can, for example, be achieved by a deep N type implant in the region of NMOS transistors consisting of phosphorous with an implant dose ranging from 1×1011/cm2, to 1×1014/cm2 and an energy ranging from 250 KeV to 2 MeV. This implant is annealed at temperatures ranging from 900° C. to 1150° C. for 15 seconds to 2 hours.
Diodes for use with NMOS are formed in an area adjoining the NMOS, next to the well tap in the same isolation area. This area containing the diode also receives the n-well implant, which is used to form the n-well region for PMOS transistors. This is done by using, for example, phosphorous or arsenic ions with doping in the range of 1E11/cm2 and 5E14/cm2 at an implant energy in the range of 25 KeV and 400 KeV. The N type isolation implant and the N-well implant form a contiguous N type semiconductor region. An n+ contact region is formed in the implanted n-well region to provide the ohmic contact for the cathode. The anode region is formed by the p+ implant that is used for making the p+ source/drain regions for the PMOS transistor. The anode and cathode regions are formed using the source and drain implants for PMOS and NMOS, respectively. The implant dose and energy are determined by the electrical characteristics of the transistor. A silicide strap formed by in situ self-aligned silicidation of silicon by reacting it with titanium, cobalt, nickel, or any other suitable metal is formed to short the cathode of the diode with the well contact of the NMOS. In an embodiment of the disclosed invention a metallic conductor is required, typically a metal 1 copper layer.
In a PMOS implementation shown in
Another type of diode that may be used in practicing this invention is an integrated diode. These diodes are formed by the contact of n-type and p-type polysilicon to underlying silicon of opposite polarity. The polysilicon layers are the same as those that are used to build the gate of MOS transistors. These diodes are formed by preventing the formation of the gate oxide underneath the transistor gates, or by removing the oxide prior to the deposition of polysilicon. The voltage across the diodes is adjusted by controlling the doping profiles in silicon and programming the area of the diodes.
A layer of polysilicon is next deposited on the wafer, and the regular CMOS process steps are conducted. The polysilicon layer is doped to form a conductivity region n+ and p+ for NMOS and PMOS transistor gates, respectively. The ohmic electrical connection between the diode terminal and the well terminal is accomplished with the help of the self-aligned silicide, which is an essential part of the CMOS process step. In an alternate embodiment of the invention, the gate oxide underneath the polysilicon on top of the diode region is damaged by the appropriate dopant type to change the electrical characteristic of the oxide, to allow it to conduct electrical charge. For NMOS transistor, a phosphorous or arsenic implant, and for PMOS transistor, a boron implant, of dose 1×1013 to 1×1016 atoms/cm2 with an energy ranging from 25 KeV to 200 KeV is used to implant the polysilicon layer and damage the underlying gate oxide in the region of the diode and form an electrically conducting electrode.
Yet another type of diode that may be used in the invention is the in-line polysilicon diode. These are presently considered to be the most area and process efficient structures and are created by implanting n-type and p-type dopant separated laterally in a line of polysilicon. The voltage drop across the diodes is controlled by programming the location of the n-type and p-type implants used to form the diodes.
The layer of polysilicon is implanted with n+ and p+ on two sides having a lateral separation. A diode is formed at the intersection of the two regions. The forward characteristics of this diode are dependent upon the level of doping of the two impurity types in polysilicon and the separation between the two regions. Coincident mask layers (Is=0) or overlapping mask layers (negative Is) produce diodes having very high reverse leakage and low forward drop. On the other hand, with increasing separation of the n+ and p+ regions, the reverse leakage of the diode decreases and the forward drop across the diode decreases. The space between the n+ and p+ implant regions in polysilicon is, for example, between −0.5 micron (overlap) to 2.0 micron (separation) and it is programmed during mask layout. The lateral-masking dimension controls the barrier height of polysilicon diode. Alternately, a polysilicon layer is uniformly implanted in the region of the diode by an N-type P-type dopant, as the case may be, with a lower implant dose, such as 1×1013-5×1015 atoms/cm2 of appropriate doping species, and the desired region for the formation of anode (cathode) is implanted with a heavier dose of the P (N) type species, e.g. with a dose of 2×1013/cm2-5×1016 atoms/cm2. This arrangement does not require alignment of the N and P type implants and relies strictly on the dopant concentration to determine the diode characteristics.
The isolation of the NMOS transistor obtained by this technique leaves the N type layer underneath the NMOS transistor floating, i.e. not in ohmic contact with any node with a well-defined voltage. The most appropriate application of this invention is for systems using VDD at or below 1.0V, where the possibility of any parasitic action due to incidental forward biasing of any p-n junction is negligible.
In yet another embodiment of the invention use is made of Schottky diodes. The Schottky diodes are formed at the interface of a layer of a metallic material, for example titanium, titanium nitride, or relevant silicides, and n-type or p-type silicon. The Schottky diodes can be formed on n-type and p-type silicon by carefully selecting the work function of the metallic layer and adjusting the Fermi level of the silicon by control of doping. The voltage across the diodes can be adjusted by changing the doping in the well and the diode area.
In one embodiment of the invention, the well biasing scheme is used only for PMOS transistors that are built in a CMOS technology. The PMOS transistors are isolated as they are formed in the n-well regions, while NMOS transistors are formed in the p-well regions that are electrically connected to one another because they are formed over p-type silicon substrate as the starting substrate material.
To control the substrate voltage, one or more diode types can be used in a design by connecting them in series or parallel to obtain the appropriate voltage at the substrate, with appropriate temperature coefficient. Also, the threshold voltage control can be applied to either or NMOS or PMOS transistor, or to both transistors with appropriate diode types. The invention covers the three cases, namely dynamic control of threshold voltage for NMOS only, for PMOS only, and that of both NMOS and PMOS.
For the purpose of explanation, it is now assumed that the operating voltage VDD is 1.0V for a CMOS circuit. A CMOS buffer uses an NMOS transistor having a source-substrate diode area of Asn and current-voltage characteristics that are as follows:
V f =n n0 *Vt*In(I diode /I sn0) (1)
where nn0 is the ideality factor that may vary, depending on the specific implementation of the diodes, between a value close to one for source/substrate diodes, 1.1-1.2 for Schottky diodes, and close to 2 for certain ploy diodes;
An external diode Dex is used as a control device ZC 260, of
where Iex0 is the diode saturation current of the external diode. Because the two diodes are in series, the same current flows through the diodes. The sum of the voltages across the two devices is equal to VDD.
V DD =V f V f
Because Isn0 is fixed by the NMOS transistor characteristics, the voltage across the external diode is varied by changing diode saturation current Iex0 which is a product of the current density and the area. If the voltage drop across the two diodes is exactly equal, then the substrate voltage of the NMOS transistor is at 0.5V when the gate is at 1.0V. Reducing Iex0 results in decreased voltage drop Vf across the source-substrate diode and, hence, the threshold voltage of the NMOS transistor.
In an exemplary embodiment of the invention, for a power supply voltage of 1.0V, the control circuit 260 comprises a single bulk-silicon diode capable of sustaining a forward drop of between 0.5V to 0.7V when connected in series with the substrate-to-source diode. The resulting voltage drop across the substrate-to-source diode is 0.5 to 0.3V. In one embodiment of the invention, the control circuit 260 is formed from a diffused diode. In another embodiment of the invention, the control circuit is formed from a single polysilicon diode or two polysilicon diodes connected in series. For a power supply voltage of 0.9V, the bias control circuit 260 should provide a forward drop of in the range of 0.5-0.3V across the substrate-to-source diode.
In the exemplary case of a power supply of 1.5V, the NMOS and PMOS transistors are designed typically with a threshold voltage of 0.45V, with an upper limit of 0.7V and a lower limit of 0.3V. These numbers refer to the magnitude of the voltage only because the threshold voltage of the PMOS devices is a negative quantity. The configuration of the control circuit ZC 260 depends upon the operating voltage. For a power supply voltage of 1.5V, the configuration of this control circuit ZC 260 is accomplished by using two or three diodes in series. The two diodes are made in polysilicon by doping the polysilicon with an n+ and p+ implant and the using silicide to connect the gate of the NMOS transistor to the anode, or for a PMOS transistor to the cathode of the first diode. Similarly, the cathode of the first diode is connected to the anode of the second diode with silicide. Because silicide is formed on the polysilicon layer in a self-aligned manner, it does not require any contact hole or metal to be formed on the transistor. The diodes can also be formed on silicon substrate. Furthermore, a combination of diodes formed on polysilicon and silicon substrates can be used. In an implementation of invention in SOI technology, the diode is formed on isolated islands insulated by oxide or by a set of polysilicon diodes, as described above.
A person skilled in the art would note that, while the description provided herein is for VDD voltages below 1.5V, the same apparatus and method can be implemented with appropriate modifications for VDD voltages higher than that. Furthermore, the descriptions herein are provided as examples of the invention and by no means should be viewed as limiting the scope of the disclosed invention. While NMOS implementations are shown herein, the invention can also be used for PMOS transistors. The use of a control circuit, such as a diode, connected between the gate and the substrate, as described herein, may also be useful in conjunction with memory designs and, particularly, with memories that have significant leakages, such as random access memories (RAMs) and dynamic RAMs (DRAMs).
An exemplary and non-limiting circuit layout that includes a MOS transistor in combination with a control circuit 260A is shown in
Another configuration employing multiple diodes is shown in
The preferred capacitor value for use in controlling the voltage waveform is related to the capacitance of the gate oxide. This capacitance value ranges between 0.01 to 100 times the value of the gate capacitance. An important factor in designing the feed-forward capacitor is the total capacitance of the well to other portions of the device. This capacitance is typically similar in magnitude to the gate capacitance. Ideally, the capacitance voltage division is identical to the voltage division established by the diodes.
In another embodiment of the invention, performance concerns may cause a deviation from that standard. Multiple methods can be used to realize this capacitance. The resistors and capacitors shown in
Where two or more of the same type MOS gates, for example n-channel gates, are connected in series, e.g. NAND gate, the leakage current from the MOS gates in series is significantly reduced. Similarly, in circuits where two or more p-channel gates are connected in series, e.g. NOR gate, the leakage current from the MOS gates in series is significantly reduced. In such cases, it may not be necessary to configure the MOS gates connected in series with the control circuit Zc. However, for two or more MOS gates connected in parallel having a control circuit Zc for each of the MOS gates reduces their leakage current, as taught by the invention. In one embodiment of the invention the MOS gates connected in parallel share a common isolated well, i.e. P-well for n-channel devices and N-well for p-channel devices, and a single control circuit Zc.
Although the invention is described herein with reference to the preferred embodiment, one skilled in the art will readily appreciate that other applications may be substituted for those set forth herein without departing from the spirit and scope of the present invention. Accordingly, the invention should only be limited by the Claims included below.
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|U.S. Classification||438/199, 327/265, 438/202, 257/360|
|Cooperative Classification||H01L27/0727, H03K19/0005, H03K19/0016, H03K19/00361, H01L29/78, H01L27/0629, H01L27/1203|
|European Classification||H01L29/78, H01L27/06D4V, H01L27/07F4, H03K19/00L, H03K19/003J4, H03K19/00P6|