|Publication number||US8106720 B2|
|Application number||US 12/093,704|
|Publication date||Jan 31, 2012|
|Filing date||Nov 1, 2006|
|Priority date||Nov 18, 2005|
|Also published as||CN101310436A, CN101310436B, EP1952530A1, US8736395, US20090219105, US20120119840, WO2007057804A1|
|Publication number||093704, 12093704, PCT/2006/54040, PCT/IB/2006/054040, PCT/IB/2006/54040, PCT/IB/6/054040, PCT/IB/6/54040, PCT/IB2006/054040, PCT/IB2006/54040, PCT/IB2006054040, PCT/IB200654040, PCT/IB6/054040, PCT/IB6/54040, PCT/IB6054040, PCT/IB654040, US 8106720 B2, US 8106720B2, US-B2-8106720, US8106720 B2, US8106720B2|
|Inventors||Mihai A. T. Sanduleanu, Ram P. Aditham, Eduard F. Stikvoort|
|Original Assignee||Nxp B.V.|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (14), Referenced by (2), Classifications (8), Legal Events (3)|
|External Links: USPTO, USPTO Assignment, Espacenet|
The present invention relates to a polar modulation apparatus, wherein phase modulation and amplitude modulation components of an input signal are processed in separated paths.
In current power amplifier (PA) designs, linearity and power efficiency are important requirements. There are several parameters affecting the linearity and efficiency requirements, such as compression point, output power, available gain or accuracy, which can be expressed by an error vector magnitude (EVM). It is almost impossible to optimize all the design parameters in the same time. For instance, efficiency and linearity requirements are two contradictory requirements. In principle, increased linearity for high power levels results in less power efficiency and, on the other hand, increased efficiency for low power levels results in poor linearity.
The above problem becomes even more demanding for wireless communication systems having amplitude and phase modulation, e.g., quadrature amplitude modulation (QAM). Especially for wireless communication systems using orthogonal frequency division multiplex (OFDM) as modulation scheme, the above problem gets even worse due to the fact that OFDM signals possess high peak to average ratios (e.g. 10 dB) which determines another design parameter of the PA design. Such high peak to average ratios require class A and AB driving schemes for the PAs for said OFDM communication systems. However, using class A and AB leads to a significant reduction of efficiency of the PAs. For example, Wireless Local Area Network (WLAN) PAs need to provide power levels in the order of 19 to 21 dBm at the output and have to meet EVM requirements with a power aided efficiency (PAE) of 20 percent or higher.
Polar modulation technology has been developed to facilitate system design for solving the above efficiency requirements. A polar modulator can independently process a carrier's amplitude and phase signals, typically working together with a non-linear power amplifier operating in switched mode. The elimination of the linear operation requirement enables power amplifier efficiency to be maximized for each modulation standard. Under a polar modulation scheme, multimode operation may be achieved by digital switching.
US2004/0219891A1 discloses a polar modulation transmitter circuit with reduced adjacent channel power ratio (ACPR) in its output signal by controlling the relative delay between its envelope and phase modulation operations based on direct and indirect feedback measurement of the output signal's ACPR. An extended transmit power control range is provided by using a staged amplifier circuit which includes a driver amplifier operating in combination with a power amplifier circuit to impart desired envelope modulation. Scaled envelope modulation signals are generated from input envelope modulation information signal by providing a modulated supply signal to the power amplifier circuit.
Other concepts use the CORDIC algorithm for generating the amplitude/phase components and combining the two signals at radio frequency (RF), i.e. in the last stage. To achieve this, output transistors have been binary weighted in emitter areas and switched on or off with a digital code representing the amplitude modulation. This concept allows 80 dB dynamic range power control via attenuation and bias control. The internal PA is a broadband PA with wideband amplitude modulation. This solution results in a programmable and configurable solution with the ability to correct for distortion in a digital manner. The output stage operates in class-E, which is enabled by the operation of an output filter and matching circuit. A reactance compensation technique allows broadband matching and the required class E of operation. However, disadvantages of this approach are summarized below.
The measured efficiency of the PA is 38% despite of the class E operation. Moreover, chokes or large resistors are required for providing a correct matching at the input of the PA, which precedes the switches. Large resistors that provide for the bias current in the PA should be used in the bias circuit such that the temperature dependency of the bias current does not produce thermal runaway. However, large resistors or at least large chokes are bulky and difficult to integrate. Additionally, switching on or off the transistors at the output, for amplitude modulation will change the output impedance and therefore the output matching conditions between the PA and the antenna. This can result in loss of power efficiency.
It is therefore an object of the present invention to provide a polar modulation apparatus and method, which enable tracking of fast amplitude modulated signals at reduced costs.
The invention is defined by the independent claims. Dependent claims The dependent claims define advantageous embodiments.
Accordingly, a new concept of a polar modulation is provided which uses a static DC-DC converter and a power, efficiency, or linearity controlled output power amplifier. Additionally, the proposed bias control via the bias input enables enhanced power control and class-operation control. The proposed solution thus can be tailored to different input power levels and efficiency requirements. As the DC-DC converter at the output of the power amplifier can be used as a static converter, there is no need for agile AM tracking any longer. The DC-DC converter can however still solve some envelope tracking function if necessary for OFDM applications. However, no large bandwidth is required. Fast varying AM modulated signals can be tracked, bearing in mind that the bandwidth of the common-mode loop is in the range of e.g. 1 GHz.
Moreover, the above solution leads to an improved linearity of the differential power amplifier means, since no extra switching components are required at the output of the power amplifier circuitry due to the fact that the DC-DC converter is a static converter.
The input of the amplitude modulation component can have a constant biasing part which helps in controlling the class of operation of the differential power amplifier circuitry tailored for different input powers and efficiency requirements. Furthermore, the input power of the phase modulation component can be held constant and the output power of the differential power amplifier circuitry can be controlled by the amplifying means. This provides an improved control range of the output power (e.g. −50 dBm . . . +30 dBm).
The amplifying circuitry may comprise at least one current amplifier stage with unity voltage gain. Therefore, the power gain of the amplifier stages is equal to the current gain and can be digitally controlled. Controlling the gain of the stages thus operates directly on the power gain and thereafter the output power of the differential power amplifier means.
According to a first aspect, the bias control circuitry may comprise push-pull circuit means connected as a driver circuit to the differential power amplifier means. The phase modulation component can be amplified by the amplifying stages and applied to the push-pull output driver. In the push-pull driver, the amplitude modulation component can be applied as a common-mode signal that modulates the common-mode current of the differential power amplifier means. As a specific example, the amplitude modulation signal may be applied to the push-pull circuit means as a common mode signal adapted to modulate the common-mode current of the differential power amplifier circuitry based on a current mirroring effect.
According to a second aspect, the bias control circuitry may comprise mixer circuit means for adding the amplitude modulation component to the common-mode current of the differential power amplifier means. According to an example, the mixer circuit means may comprise a Gilbert cell. This second aspect provides the advantage that the differential power amplifier circuitry can be implemented as a stand-alone discrete component, while the mixer circuit means can provide the required extra amplitude modulation input for the discrete differential power amplifier means.
According to a third aspect, the bias control circuitry can be adapted to supply the amplitude modulation component to a cascode circuit of the differential power amplifier means. This measure is advantageous for CMOS (Complementary Metal Oxide Semiconductor) applications.
In all above aspects, the bias control circuitry can be adapted to be based on a digital control. Thereby, digitally controlled parameters (e.g. power, efficiency, modulation and linearity) can provide an accurate monitoring of the differential power amplifier means.
Additionally, power control means may be provided for controlling power of the polar modulation apparatus by changing at least one tail current of the amplifying means.
The in-phase component and a quadrature-phase component of the input signal may be generated by baseband digital processing means, and converted by conversion means to generate the phase modulation component. This may be achieved by providing at least one of an IQ mixer circuit, a zero intermediate frequency transmitter circuit and a fractional N synthesizer phase locked loop circuit.
The present invention will now be described based on embodiments with reference to the accompanying drawings, in which:
The embodiments will now be described in connection with a polar modulator arrangement, which uses an IQ modulation in a wireless communication system, such as Bluetooth, UWB (Ultra-Wideband), WLAN (Wireless Local Area Network) or GSM EDGE (Global System for Mobile communication Enhanced Data rates for GSM Evolution).
In summary, a polar modulation apparatus and method have been described, in which a polar-modulated signal is generated based on separately processed phase modulation (PM, EM) and amplitude modulation (AM) components of an input signal. An amplified polar modulated output signal is generated in accordance with the phase modulation and amplitude modulation components by using a differential power amplifier circuitry and supplying an amplified phase modulation component to a differential input of the differential power amplifier means. A bias input of the differential power amplifier circuitry is controlled based on the amplitude modulation component, so as to modulate a common-mode current of the differential power amplifier means. Thereby, a new concept of a polar modulator with static DC-DC converter and power and/or efficiency and/or linearity controlled output power amplifier can be achieved. In the conventional polar modulator approach a fast DC-DC converter is used for tracking the envelope of the signal. This conventional approach is hampered by the tracking bandwidth of the DC-DC converter and the price of this device. The proposed solution according to the above embodiments circumvents the disadvantages encountered in the DC-DC converter approach. Additionally, the proposed power and operation class control provides a solution tailored to different input power levels and efficiency requirements. Digitally controlled parameters (power, efficiency, modulation and/or linearity) can be used to provide an accurate monitoring of the PA.
It is noted that the present invention is not restricted to the above preferred embodiments, but can be applied to any polar modulation and power amplifier architecture which is based on a processing of separated amplitude and phase modulation signals. Hence, the preferred embodiments may vary within the scope of the attached claims.
The term “comprises” or “comprising” when used in the specification including the claims is intended to specify the presence of stated features, means, steps or components, but does not exclude the presence or addition of one or more other features, means, steps, components or group thereof. Further, the word “a” or “an” preceding an element in a claim does not exclude the presence of a plurality of such elements. Moreover, any reference sign does not limit the scope of the claims.
|Cited Patent||Filing date||Publication date||Applicant||Title|
|US6137354||May 18, 1998||Oct 24, 2000||Omnipoint Corporation||Bypassable amplifier|
|US6141541||Dec 31, 1997||Oct 31, 2000||Motorola, Inc.||Method, device, phone and base station for providing envelope-following for variable envelope radio frequency signals|
|US6194963||Nov 18, 1998||Feb 27, 2001||Ericsson Inc.||Circuit and method for I/Q modulation with independent, high efficiency amplitude modulation|
|US7072626 *||Apr 30, 2003||Jul 4, 2006||Telefonaktiebolaget Lm Ericsson (Publ)||Polar modulation transmitter|
|US7366482 *||Aug 10, 2004||Apr 29, 2008||Matsushita Electric Industrial Co., Ltd.||Transmission device, transmission output control method, and radio communications device|
|US7383027||Jan 25, 2005||Jun 3, 2008||Matsushita Electric Industrial Co., Ltd.||Transmission circuit|
|US7428407 *||Aug 5, 2005||Sep 23, 2008||Infineon Technologies Ag||Amplitude modulator, in particular for mobile radio, and a method for modulation of a signal|
|US7555057 *||Dec 31, 2003||Jun 30, 2009||Texas Instruments Incorporated||Predistortion calibration in a transceiver assembly|
|US20020024142||Aug 17, 2001||Feb 28, 2002||Mitsuru Sekiguchi||Semiconductor device and manufacturing method of the same|
|US20040092236||Oct 16, 2003||May 13, 2004||Kiyoshi Irie||Semiconductor integrated circuit device and wireless communication system|
|US20040219891||Apr 30, 2003||Nov 4, 2004||Aristotle Hadjichristos||Polar modulation transmitter|
|US20040232988||May 19, 2004||Nov 25, 2004||Toshifumi Nakatani||High frequency differential circuit, differential amplifier, differential mixer, differential oscillator, and radio circuit using same|
|US20050271161 *||Aug 27, 2004||Dec 8, 2005||Texas Instruments Incorporated||Digital amplitude modulation|
|JP2005295533A||Title not available|
|Citing Patent||Filing date||Publication date||Applicant||Title|
|US8736395 *||Dec 21, 2011||May 27, 2014||Nxp, B.V.||Polar modulation apparatus and method with common-mode control|
|US20120119840 *||Dec 21, 2011||May 17, 2012||Sanduleanu Mihai A T||Polar modulation apparatus and method with common-mode control|
|U.S. Classification||332/145, 332/151, 455/102|
|International Classification||H04B1/02, H03C1/50, H03C3/38|
|Dec 1, 2011||AS||Assignment|
Owner name: NXP B.V., NETHERLANDS
Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:SANDULEANU, MIHAI A. T.;ADITHAM, RAM P.;STIKVOORT, EDUARD F.;SIGNING DATES FROM 20111017 TO 20111025;REEL/FRAME:027312/0250
|May 31, 2015||FPAY||Fee payment|
Year of fee payment: 4
|Mar 7, 2016||AS||Assignment|
Owner name: MORGAN STANLEY SENIOR FUNDING, INC., MARYLAND
Free format text: SECURITY AGREEMENT SUPPLEMENT;ASSIGNOR:NXP B.V.;REEL/FRAME:038017/0058
Effective date: 20160218