US8587248B2 - Method for controlling a polyphase converter with distributed energy stores at low output frequencies - Google Patents

Method for controlling a polyphase converter with distributed energy stores at low output frequencies Download PDF

Info

Publication number
US8587248B2
US8587248B2 US12/933,179 US93317908A US8587248B2 US 8587248 B2 US8587248 B2 US 8587248B2 US 93317908 A US93317908 A US 93317908A US 8587248 B2 US8587248 B2 US 8587248B2
Authority
US
United States
Prior art keywords
voltage
converter
lower valve
valve branch
common mode
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active, expires
Application number
US12/933,179
Other versions
US20110018481A1 (en
Inventor
Marc Hiller
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Innomotics GmbH
Original Assignee
Siemens AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Siemens AG filed Critical Siemens AG
Assigned to SIEMENS AKTIENGESELLSCHAFT reassignment SIEMENS AKTIENGESELLSCHAFT ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: HILLER, MARC, DR.
Publication of US20110018481A1 publication Critical patent/US20110018481A1/en
Application granted granted Critical
Publication of US8587248B2 publication Critical patent/US8587248B2/en
Assigned to INNOMOTICS GMBH reassignment INNOMOTICS GMBH ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: SIEMENS AKTIENGESELLSCHAFT
Active legal-status Critical Current
Adjusted expiration legal-status Critical

Links

Images

Classifications

    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483Converters with outputs that each can have more than two voltages levels
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483Converters with outputs that each can have more than two voltages levels
    • H02M7/4835Converters with outputs that each can have more than two voltages levels comprising two or more cells, each including a switchable capacitor, the capacitors having a nominal charge voltage which corresponds to a given fraction of the input voltage, and the capacitors being selectively connected in series to determine the instantaneous output voltage
    • HELECTRICITY
    • H02GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02MAPPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00Details of apparatus for conversion
    • H02M1/0003Details of control, feedback or regulation circuits

Definitions

  • the invention relates to a method for controlling a converter with at least two phase modules having an upper and a lower valve branch having in each case two two-pole subsystems connected in series at low output frequencies.
  • Such a converter with distributed energy stores is known from the publication “Modulares Stromrichterbuch für Netzkupplungsanengine bei (2017) (2017)”, by Rainer Marquardt, Anton Lesnicar and Wegml urgen Hildinger” [Modular Converter Concept for System Coupling Application at High Voltages], printed in the conference proceedings of the ETG Conference 2002.
  • such a converter is used for a system-side and load-side converter, with these two converters being coupled to one another with distributed energy stores on the DC-voltage side.
  • FIG. 1 shows in more detail such a converter with distributed energy stores.
  • this known converter circuit has three phase modules, which are each denoted by 100 .
  • These phase modules 100 are connected electrically conductively on the DC-voltage side in each case to a connection P or N with a positive or negative DC voltage busbar P 0 or N 0 .
  • a DC voltage U d is present between these two DC voltage busbars P 0 and N 0 .
  • Each phase module 100 has an upper and a lower valve branch T 1 or T 3 or T 5 and 12 or T 4 or T 6 .
  • Each of these valve branches T 1 to T 6 has a number of two-pole subsystems 10 which are connected electrically in series.
  • valve branch T 1 . . . , T 6 .
  • Each node between two valve branches T 1 and T 2 or T 3 and T 4 or T 5 and T 6 of a phase module 100 forms a connection L 1 or L 2 or L 3 of this phase module 100 on the AC-voltage side.
  • FIG. 2 shows in more detail an embodiment of a known two-pole subsystem 10 .
  • the circuit arrangement shown in FIG. 3 represents a functional equivalent variant.
  • These two subsystems 10 and 11 are described in more detail in DE 101 03 031 A1, which laid-open specification also describes the way in which said subsystems operate.
  • FIG. 4 A further embodiment of a two-pole subsystem 20 is shown in more detail in FIG. 4 .
  • This embodiment of the two-pole subsystem 20 is known from DE 10 2005 041 087 A1.
  • the design of this two-pole subsystem 20 and the way in which it operates are described in detail in this laid-open specification, and therefore no explanation in relation to this is necessary at this juncture.
  • the voltages u 1 (t), . . . , u 6 (t) at the valve branches T 1 , . . . , T 6 also referred to as valve branch voltage u 1 (t), . . . , u(t), comprise a DC variable 1 ⁇ 2U d and an AC voltage variable u 10 (t), u 20 (t), u 30 (t).
  • This AC voltage variable u 10 (t) or u 20 (t) or u 30 (t) has, firstly a frequency and an amplitude of a desired output voltage of the converter.
  • AC variables u 10 (t), u 20 (t) and u 30 (t) are related to a fictitious mid-point 0 between the two DC voltage busbars P 0 and N 0 , as shown in FIG. 1 .
  • the voltage u 1 (t) or u 2 (t) or u 3 (t) or u 4 (t) or u 5 (t) or u 6 (t) of a valve branch T 1 or T 2 or T 3 or T 4 or T 5 or T 6 must therefore always be positive since all of the two-pole subsystems 10 of a valve branch T 1 , . . . , T 6 which are connected in series can generate only a short circuit or a positive voltage at the output terminals X 1 and X 2 of each two-pole subsystem 10 , irrespective of the valve branch current direction in all switching states. Owing to the structure of these two-pole subsystems 10 , 11 and 20 , negative voltages are not possible.
  • valve voltage u 1 (t) or u 2 (t) or u 3 (t) or u 4 (t) or u 5 (t) or u 6 (t) of each valve branch T 1 or T 2 or 13 or T 4 or 15 or 16 can vary between zero and n times a capacitor voltage U c of the n independent energy stores 9 and, respectively, 29 , 30 .
  • FIG. 5 shows a characteristic of the valve branch voltage u 1 (t) and of the valve branch current i 1 (t) of the valve branch T 1 of the phase module 100 of the polyphase converter shown in FIG. 1 in a graph over time t. If the two characteristics are multiplied by one another, the time characteristic of an instantaneous power P T1 (t) of this valve branch T 1 is produced, which is illustrated in a graph over time t in FIG. 6 . If this instantaneous power P T1 (t) of the valve branch T 1 is integrated over a period of the valve branch voltage u 1 (t) (corresponds to the areas below the curved sections of the curve of the instantaneous power P T1 (t)), in the steady state the value zero is always reached.
  • each energy store 9 of each valve branch T 1 , . . . , T 6 of the polyphase converter shown in FIG. 1 and therefore of this polyphase converter is constant in the steady state.
  • these two-pole subsystems 10 and 11 and 20 also do not require an active power feed to the respective DC voltage connections of the energy stores 9 and 29 , 30 , respectively.
  • each energy content of each energy store 9 or 29 , 30 of the two-pole subsystems 10 , 11 and 20 , respectively, of each valve branch T 1 , . . . , T 6 is advantageously dimensioned in accordance with the maximum required energy deviation. It is necessary here to take into account the fact that the voltage ripple ⁇ U which is superimposed on the steady-state voltage mean value in the energy stores 9 and 29 , 30 should not overshoot a maximum predetermined limit value. This maximum voltage is determined by the dielectric strength of the semiconductor switches and energy stores 9 and 29 , 30 which can be switched off and are used in the two-pole subsystems 10 , 11 and 20 , respectively, and also by means of regulation technology.
  • a decisive factor in the dimensioning of the energy stores 9 and 29 , 30 is the output frequency of the polyphase converter shown in FIG. 1 .
  • This relationship between the voltage ripple ⁇ U and the output frequency f of the polyphase converter shown in FIG. 1 is illustrated in a graph shown in FIG. 7 .
  • This graph shows a hyperbolic curve A for the voltage ripple of an energy store (continuous line) and a hyperbolic curve B for the voltage ripple when using three partial energy stores in parallel per energy store 9 or 29 , 30 , i.e. three times the intermediate-circuit capacitance (dashed line).
  • the value of an energy store 9 or 29 , 30 of a two-pole subsystem 10 , 11 or 20 must be a multiple greater.
  • the energy store 9 or 29 , of the two-pole subsystems 10 , 11 or 20 would need to be dimensioned to be a factor of 25 greater.
  • the invention is now based on the object of specifying a method for controlling a polyphase converter with distributed energy stores, which enables operation at low output frequencies up to the DC operating mode.
  • a method for controlling a polyphase converter at a low output frequency comprising at least two phase modules, each phase module having an upper and a lower valve branch, with each of the upper and a lower valve branches each comprising at least two two-pole subsystems connected in series, the method comprising superimposing a common-mode voltage on a setpoint value of a voltage of the upper and lower valve branches such that a sum of the voltages of the upper and lower valve branch of each phase module is equal to an intermediate circuit voltage of the polyphase converter.
  • a common mode voltage is superimposed on a setpoint value of all of the valve branch voltages of the polyphase converter with distributed energy stores. Since this superimposed AC voltage simultaneously alters the potentials of all three connections, on the AC-voltage side, of the polyphase converter with distributed energy stores in comparison with the potentials of the DC voltage busbars thereof, this modulated AC voltage is referred to as the common mode voltage.
  • the superimposed common mode voltage ensures that the line-to-line output voltages of the polyphase converter with distributed energy stores remain unaffected.
  • the common mode voltage is predefined in such a way that the voltage ripple of all of the energy stores 9 and 29 , 30 does not overshoot a predetermined maximum value.
  • the maximum voltage at the energy stores likewise remains below a predetermined maximum value, which is selected in accordance with the dielectric strength of the semiconductors and energy stores.
  • the common mode voltage is predefined in such a way that in each case a predetermined maximum value for the valve branch currents is not overshot.
  • the amplitude of the common mode voltage is inversely proportional to the rise in the output frequency. This means that this common mode voltage is only effective in a frequency band below a rated frequency.
  • FIG. 1 shows a circuit diagram of a known three-phase converter with distributed energy stores
  • FIGS. 2 to 4 each show an equivalent circuit diagram of a two-pole subsystem of the converter shown in FIG. 1 ,
  • FIG. 5 illustrates a graph over time t of a valve branch voltage and an associated valve branch current
  • FIG. 6 illustrates a graph over time t of an instantaneous power corresponding to the valve branch voltage and valve branch current shown in FIG. 5 over time t
  • FIG. 7 shows a graph of the voltage ripple as a function of the output frequency of the converter shown in FIG. 1 .
  • FIG. 8 shows a graph over time t of a valve branch voltage of the converter shown in FIG. 1 at an output frequency of 50 Hz and 5 Hz,
  • FIG. 9 shows a graph over time t of associated instantaneous powers
  • FIG. 11 shows a graph over time t of three valve branch voltages of the converter shown in FIG. 1 , in each case with a common mode voltage which is not equal to zero, and
  • FIG. 12 shows an advantageous embodiment of the three-phase converter shown in FIG. 1 .
  • each valve branch T 1 , . . . , T 6 at each time always produces half the DC voltage U d between the DC voltage busbars P 0 and N 0 which are common to all of the phase modules 100 .
  • a sinusoidal component with a predetermined frequency and a desired amplitude of a converter output voltage u 10 (t), u 20 (t) or u 30 (t), which is related to a fictitious mid-point between the voltage busbars P 0 and N 0 is generally superimposed on this direct current variable.
  • a common mode voltage u CM (t) is superimposed on these valve branch voltages u 1 (t), . . . , u 6 (t) in such a way that the line-to-line output voltages continue to be excluded thereby.
  • the following equations then apply to the time characteristics of these valve branch voltages u 1 (t), . . . , u 6 (t).
  • output converter currents i L1 (t), i L2 (t) and i L3 (t), also referred to as load currents i L1 (t), i L2 (t) and i L3 (t), and therefore also the valve branch powers P T1 (t), . . . , P T6 (t) of each valve branch T 1 , . . . , T 6 during operation at a low output frequency f up to an output frequency f 0 (DC operating mode) in the time characteristic now only have very few zero points, or no zero points at all ( FIG. 9 ), the balancing of the energy stores 9 within a voltage branch T 1 , . . .
  • the energy stores 9 and 29 , 30 of the subsystems 10 , 11 and 20 , respectively of the upper valve branches T 1 , T 3 and T 5 adjust their energy content to one another.
  • the common mode voltage u CM (t) can be used irrespective of the type of energy compensation (passive or active). It is only possible to limit the energy deviation of the energy stores by compensating currents in such a way that the level of these compensating currents does not result in unfavorable overdimensioning of the semiconductors by virtue of a simultaneous shift, as a result of a common mode voltage u CM (t), in the potentials of the converter output voltages u 10 (t), u 20 (t) and u 30 (t).
  • the additional valve branch current results in increased on-state losses and switching losses in the semiconductor switches which can be disconnected of the two-pole subsystems 10 , 11 and 20 used.
  • more favorable dimensioning of the energy stores of the subsystems 10 , 11 and 20 used is achieved, i.e., this disadvantage is considered to be insignificant in comparison with the advantage (more favorable energy store dimensions).
  • the converter known from the conference proceedings relating to the ETG Conference 2002 which converter has a three-phase converter with distributed energy stores as shown in FIG. 1 on the system and load side, can be used as a drive converter which can be run up from standstill.
  • the energy stores 9 and 29 , 30 of the subsystems 10 , 11 and 20 used can be dimensioned in optimum fashion.

Abstract

The invention relates to a method for controlling a multi-phase power converter having at least two phase modules (100) comprising valve branches (T1, . . . , T6) having bipolar subsystems (10, 11) connected in series, at low output frequencies (f). According to the invention, a target value (u1 (t), . . . , u6 (t)) of a valve branch voltage overlaps a common-mode voltage (uCM(t)) such that a sum of two valve branch voltages (u1 (t), U2 (t) or U3 (t), U4 (t) or U5 (t), U6 (t)) of each phase module (100) equals an intermediate circuit voltage (Ud) of said multi-phase power converter. In this manner a known converter having a triphase power converter comprising distributed energy accumulators on the grid and load side, or merely on the load side, may be utilized as a drive converter, which may start up from the idle state.

Description

CROSS-REFERENCES TO RELATED APPLICATIONS
This application is the U.S. National Stage of International Application No. PCT/EP2008/065270, filed Nov. 11, 2008, which designated the United States and has been published as International Publication No. WO 2009/115141 A1 and which claims the priority of German Patent Application, Serial No. 10 2008 014 898.9, filed Mar. 19, 2008, pursuant to 35 U.S.C. 119(a)-(d).
BACKGROUND OF THE INVENTION
The invention relates to a method for controlling a converter with at least two phase modules having an upper and a lower valve branch having in each case two two-pole subsystems connected in series at low output frequencies.
Such a converter with distributed energy stores is known from the publication “Modulares Stromrichterkonzept für Netzkupplungsanwendung bei hohen Spannungen”, by Rainer Marquardt, Anton Lesnicar and Jüml urgen Hildinger” [Modular Converter Concept for System Coupling Application at High Voltages], printed in the conference proceedings of the ETG Conference 2002. In this publication, such a converter is used for a system-side and load-side converter, with these two converters being coupled to one another with distributed energy stores on the DC-voltage side.
FIG. 1 shows in more detail such a converter with distributed energy stores. In accordance with this circuit arrangement, this known converter circuit has three phase modules, which are each denoted by 100. These phase modules 100 are connected electrically conductively on the DC-voltage side in each case to a connection P or N with a positive or negative DC voltage busbar P0 or N0. A DC voltage Ud is present between these two DC voltage busbars P0 and N0. Each phase module 100 has an upper and a lower valve branch T1 or T3 or T5 and 12 or T4 or T6. Each of these valve branches T1 to T6 has a number of two-pole subsystems 10 which are connected electrically in series. In this equivalent circuit diagram, four subsystems 10 are illustrated per valve branch T1, . . . , T6. Each node between two valve branches T1 and T2 or T3 and T4 or T5 and T6 of a phase module 100 forms a connection L1 or L2 or L3 of this phase module 100 on the AC-voltage side.
FIG. 2 shows in more detail an embodiment of a known two-pole subsystem 10. The circuit arrangement shown in FIG. 3 represents a functional equivalent variant. These two subsystems 10 and 11 are described in more detail in DE 101 03 031 A1, which laid-open specification also describes the way in which said subsystems operate.
A further embodiment of a two-pole subsystem 20 is shown in more detail in FIG. 4. This embodiment of the two-pole subsystem 20 is known from DE 10 2005 041 087 A1. The design of this two-pole subsystem 20 and the way in which it operates are described in detail in this laid-open specification, and therefore no explanation in relation to this is necessary at this juncture.
The number of independent energy stores 9 and 29, 30 which are connected in series between a positive connection P and a connection L1 or L2 or L3 of a phase module 100 on the AC-voltage side is referred to as the series operating cycle n. It is advantageous here, but not absolutely necessary, to implement the same series operating cycle n between a connection L1 or L2 or L3 on the AC-voltage side and a negative connection N of a phase module 100. As shown in FIG. 1, each valve branch T1, . . . , T6 of the polyphase converter has four two-pole subsystems 10, which are connected electrically in series. Since these subsystems 10 each have only one independent energy store 9, a series operating cycle of n=4 results. If, instead of these subsystems 10, four subsystems 20 are used as shown in FIG. 2, this results in a series operating cycle n=8 since each subsystem 20 has two independent energy stores 29 and 30.
For the following explanation it is assumed that all of the energy stores 9 of the subsystems 10 of each valve branch T1, . . . , T6 of this polyphase converter are each charged to the same voltage Uc. A method for charging this energy store 9 is described, for example, in the conference proceedings for the ETG Conference 2002.
The voltages u1(t), . . . , u6(t) at the valve branches T1, . . . , T6, also referred to as valve branch voltage u1(t), . . . , u(t), comprise a DC variable ½Ud and an AC voltage variable u10(t), u20(t), u30(t). This AC voltage variable u10(t) or u20(t) or u30(t) has, firstly a frequency and an amplitude of a desired output voltage of the converter. These AC variables u10(t), u20(t) and u30(t) are related to a fictitious mid-point 0 between the two DC voltage busbars P0 and N0, as shown in FIG. 1. This results in sinusoidal converter output voltages u10(t), u20(t) and u30(t), wherein the following must apply for the amplitudes of the voltages u10(t), u20(t) and u30(t) related to the mid-point 0: each amplitude of an AC voltage variable u10(t), u20(t) and u30(t) should always be less than half the DC voltage Ud. The voltage u1(t) or u2(t) or u3(t) or u4(t) or u5(t) or u6(t) of a valve branch T1 or T2 or T3 or T4 or T5 or T6 must therefore always be positive since all of the two-pole subsystems 10 of a valve branch T1, . . . , T6 which are connected in series can generate only a short circuit or a positive voltage at the output terminals X1 and X2 of each two-pole subsystem 10, irrespective of the valve branch current direction in all switching states. Owing to the structure of these two- pole subsystems 10, 11 and 20, negative voltages are not possible. Therefore, the valve voltage u1(t) or u2(t) or u3(t) or u4(t) or u5(t) or u6(t) of each valve branch T1 or T2 or 13 or T4 or 15 or 16 can vary between zero and n times a capacitor voltage Uc of the n independent energy stores 9 and, respectively, 29, 30.
FIG. 5 shows a characteristic of the valve branch voltage u1(t) and of the valve branch current i1(t) of the valve branch T1 of the phase module 100 of the polyphase converter shown in FIG. 1 in a graph over time t. If the two characteristics are multiplied by one another, the time characteristic of an instantaneous power PT1(t) of this valve branch T1 is produced, which is illustrated in a graph over time t in FIG. 6. If this instantaneous power PT1(t) of the valve branch T1 is integrated over a period of the valve branch voltage u1(t) (corresponds to the areas below the curved sections of the curve of the instantaneous power PT1(t)), in the steady state the value zero is always reached. This means that the energy stores 9 of the two-pole subsystems 10 in this valve branch T1 in total do not receive or emit any energy. The same also applies to all of the other valve branches T2, . . . ,T6 of the polyphase converter shown in FIG. 1.
It follows from this that the energy content of each energy store 9 of each valve branch T1, . . . , T6 of the polyphase converter shown in FIG. 1 and therefore of this polyphase converter is constant in the steady state. For this reason, these two- pole subsystems 10 and 11 and 20 also do not require an active power feed to the respective DC voltage connections of the energy stores 9 and 29, 30, respectively.
An energy content of each energy store 9 or 29, 30 of the two- pole subsystems 10, 11 and 20, respectively, of each valve branch T1, . . . , T6 is advantageously dimensioned in accordance with the maximum required energy deviation. It is necessary here to take into account the fact that the voltage ripple ΔU which is superimposed on the steady-state voltage mean value in the energy stores 9 and 29,30 should not overshoot a maximum predetermined limit value. This maximum voltage is determined by the dielectric strength of the semiconductor switches and energy stores 9 and 29, 30 which can be switched off and are used in the two- pole subsystems 10, 11 and 20, respectively, and also by means of regulation technology. A decisive factor in the dimensioning of the energy stores 9 and 29, 30 is the output frequency of the polyphase converter shown in FIG. 1. The lower this output frequency is, the greater the energy deviation is per period in the energy store 9 or 29, 30. This means that, for a predetermined voltage ripple ΔU, the required variable of the energy stores 9 and 29, 30 of the two- pole subsystems 10, 11 and 20, respectively, would tend towards infinity in hyperbolic fashion as the frequency decreases up to the DC voltage operating mode (frequency equal to zero).
This relationship between the voltage ripple ΔU and the output frequency f of the polyphase converter shown in FIG. 1 is illustrated in a graph shown in FIG. 7. This graph shows a hyperbolic curve A for the voltage ripple of an energy store (continuous line) and a hyperbolic curve B for the voltage ripple when using three partial energy stores in parallel per energy store 9 or 29, 30, i.e. three times the intermediate-circuit capacitance (dashed line). The hyperbolic curve A shows that, starting from an output frequency f=50 Hz, the voltage ripple ΔU increases substantially as the frequency decreases. If at half the output frequency the voltage ripple ΔU should be equal to the voltage ripple ΔU at the output frequency f=50 Hz, the value of an energy store 9 or 29, 30 of a two- pole subsystem 10, 11 or 20 must be a multiple greater.
The graph in FIG. 8 shows a characteristic of the valve branch voltage u1(t) with an output frequency f=50 Hz and a characteristic of this valve branch voltage u1(t) at an output frequency of f=5 Hz over time t. The amplitude of the valve branch voltage u1(t) at an output frequency f=5 Hz has been decreased corresponding to a u/f characteristic. If a recalculation is performed taking into consideration the corresponding valve branch current in the valve branch T1 of the polyphase converter shown in FIG. 1, an associated instantaneous power PT1(t) at an output frequency f=50 Hz and f=5 Hz is produced. These two characteristics of the instantaneous power PT1(t) of the valve branch T1 are shown in the graph in FIG. 9 over time t. The energy deviation at the output frequency f=5 Hz has risen substantially in comparison with the energy deviation at the output frequency f=50 Hz. In this example illustrated, the energy deviation at f=5 Hz is 25 times greater than at f=50 Hz.
In order to produce the same voltage ripple ΔU as at the output frequency f=50 Hz in this operating point as well (f=5 Hz), the energy store 9 or 29, of the two- pole subsystems 10, 11 or 20 would need to be dimensioned to be a factor of 25 greater.
In order to arrive at a solution which is attractive in terms of size and costs, it is advantageous if the design of the energy stores 9 and 29, 30 of the two- pole subsystems 10, 11 and 20, respectively, of the valve branches T1, . . . , T6 of the polyphase converter shown in FIG. 1 is performed for a rated working point. This means that, in this rated working point, the energy deviation already results in a predetermined maximum permissible voltage ripple ΔU. For operation at low frequencies, i.e. below a rated frequency fN, up to purely DC operation (f=0 Hz), as arises when running up drives, the control methods in accordance with the prior art cannot be used for a realistic and competitive design of the energy stores 9 and 29, 30 of two- pole subsystems 10, 11 and 20 used.
SUMMARY OF THE INVENTION
The invention is now based on the object of specifying a method for controlling a polyphase converter with distributed energy stores, which enables operation at low output frequencies up to the DC operating mode.
This object is achieved according to the invention by a method for controlling a polyphase converter at a low output frequency, the converter comprising at least two phase modules, each phase module having an upper and a lower valve branch, with each of the upper and a lower valve branches each comprising at least two two-pole subsystems connected in series, the method comprising superimposing a common-mode voltage on a setpoint value of a voltage of the upper and lower valve branches such that a sum of the voltages of the upper and lower valve branch of each phase module is equal to an intermediate circuit voltage of the polyphase converter.
In accordance with the invention, a common mode voltage is superimposed on a setpoint value of all of the valve branch voltages of the polyphase converter with distributed energy stores. Since this superimposed AC voltage simultaneously alters the potentials of all three connections, on the AC-voltage side, of the polyphase converter with distributed energy stores in comparison with the potentials of the DC voltage busbars thereof, this modulated AC voltage is referred to as the common mode voltage. The superimposed common mode voltage ensures that the line-to-line output voltages of the polyphase converter with distributed energy stores remain unaffected.
In an advantageous embodiment of the method according to the invention, the common mode voltage is predefined in such a way that the voltage ripple of all of the energy stores 9 and 29, 30 does not overshoot a predetermined maximum value. As a result, the maximum voltage at the energy stores likewise remains below a predetermined maximum value, which is selected in accordance with the dielectric strength of the semiconductors and energy stores.
In a further advantageous embodiment of the method according to the invention, the common mode voltage is predefined in such a way that in each case a predetermined maximum value for the valve branch currents is not overshot. As a result, on-state losses and switching losses which occur in the semiconductor switches which can be switched off of the two-pole subsystems used are restricted to a value.
In a further advantageous embodiment of the method according to the invention, the amplitude of the common mode voltage is inversely proportional to the rise in the output frequency. This means that this common mode voltage is only effective in a frequency band below a rated frequency.
Further advantageous configurations of the method according to the invention are set forth in the dependent claims.
In order to further explain the invention, reference is made to the drawing, which is used to explain the method according to the invention in greater detail.
BRIEF DESCRIPTION OF THE DRAWING
FIG. 1 shows a circuit diagram of a known three-phase converter with distributed energy stores,
FIGS. 2 to 4 each show an equivalent circuit diagram of a two-pole subsystem of the converter shown in FIG. 1,
FIG. 5 illustrates a graph over time t of a valve branch voltage and an associated valve branch current, whereas
FIG. 6 illustrates a graph over time t of an instantaneous power corresponding to the valve branch voltage and valve branch current shown in FIG. 5 over time t,
FIG. 7 shows a graph of the voltage ripple as a function of the output frequency of the converter shown in FIG. 1,
FIG. 8 shows a graph over time t of a valve branch voltage of the converter shown in FIG. 1 at an output frequency of 50 Hz and 5 Hz,
FIG. 9 shows a graph over time t of associated instantaneous powers,
FIG. 10 shows a graph over time t of a valve branch voltage at an output frequency f=5 Hz with a common mode voltage which is unequal or equal to zero,
FIG. 11 shows a graph over time t of three valve branch voltages of the converter shown in FIG. 1, in each case with a common mode voltage which is not equal to zero, and
FIG. 12 shows an advantageous embodiment of the three-phase converter shown in FIG. 1.
DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS
As has already been described at the outset, the following equations apply to the time characteristics of the valve branch voltages u1(t), . . . , u6(t):
u1(t)˜½·Ud−u10(t),
u2(t)˜½·Ud+u10(t),
u3(t)˜½·Ud−u20(t),
u4(t)˜½·Ud+u20(t),
u5(t)˜½·Ud−u30(t),
u6(t)˜½·Ud+u30(t).
This means that each valve branch T1, . . . , T6 at each time always produces half the DC voltage Ud between the DC voltage busbars P0 and N0 which are common to all of the phase modules 100. A sinusoidal component with a predetermined frequency and a desired amplitude of a converter output voltage u10(t), u20(t) or u30(t), which is related to a fictitious mid-point between the voltage busbars P0 and N0, is generally superimposed on this direct current variable.
According to the invention, in each case a common mode voltage uCM(t) is superimposed on these valve branch voltages u1(t), . . . , u6(t) in such a way that the line-to-line output voltages continue to be excluded thereby. The following equations then apply to the time characteristics of these valve branch voltages u1(t), . . . , u6(t).
u1(t)˜½·Ud−u10(t)+uCM(t),
u2(t)˜½·Ud+u10(t)−uCM(t),
u3(t)˜½·Ud−u20(t)+uCM(t),
u4(t)˜½·Ud+u20(t)−uCM(t),
u5(t)˜½·Ud−u30(t)+uCM(t),
u6(t)˜½·Ud+u30(t)−uCM(t).
The graph in FIG. 10 illustrates a valve branch voltage u1(t) at an output frequency f=5 Hz with a common mode voltage uCM(t) which is once not equal to zero and is once equal to zero over time t. It can be seen from the signal characteristic of the valve branch voltage u1(t) with a superimposed common mode voltage uCM(t) which is not equal to zero that this common mode voltage uCM(t) is sinusoidal and the amplitude thereof is dimensioned such that the peak value û1(t) of the valve branch voltage u1(t) adheres to an upper boundary condition such that the following applies:
0<u 1(t)<U d
Since output converter currents iL1(t), iL2(t) and iL3(t), also referred to as load currents iL1(t), iL2(t) and iL3(t), and therefore also the valve branch powers PT1(t), . . . , PT6(t) of each valve branch T1, . . . , T6 during operation at a low output frequency f up to an output frequency f=0 (DC operating mode) in the time characteristic now only have very few zero points, or no zero points at all (FIG. 9), the balancing of the energy stores 9 within a voltage branch T1, . . . , T6 and therefore within an electrical period of a converter output voltage u10(t), u20(t) or u30(t) is now no longer sufficient, in contrast to operation at the rated frequency fN given the same energy store size. The periods in which a respectively constant valve current direction is applied to the valve branches T1, . . . , T6 are too long during operation without any modulated common mode voltage uCM(t). As a result, the energy stores 9 and 29, 30 of the two- pole subsystems 10, 11 and 20 used are discharged or charged excessively, which would result in an impermissibly high voltage ripple ΔU in the two- pole subsystems 10, 11 and 20.
The modulation of a common mode voltage uCM(t) forces the onset of an energy interchange between the subsystems 10, 11 and 20, which are in switching state II (Ux=Uc), of the phase modules 100 of the polyphase converter shown in FIG. 1 which are connected to the DC voltage busbars P0 and N0. If the potentials of the converter output voltages u10(t), u20(t) and u30(t) are in the vicinity of the DC voltage busbar P0 (FIG. 11), the energy stores 9 and 29, 30 of the subsystems 10, 11 and 20 of the lower valve branches T2, T4, T6 adjust their energy content to one another. If the potential of the converter output voltages u10(t), u20(t) and u30(t) is close to the DC voltage busbar N0 of the polyphase converter shown in FIG. 1, the energy stores 9 and 29, 30 of the subsystems 10, 11 and 20, respectively of the upper valve branches T1, T3 and T5 adjust their energy content to one another.
This adjustment of the energy contents results in an additional valve branch current, which is part of an existing compensating current. In this case, the energy compensation takes place passively, i.e. without any influence by a superimposed open-loop/closed-loop control system. Furthermore, it is also possible to influence the energy compensation in a targeted manner by active influencing of the valve branch currents. In this case, use is made of the method known from German patent specification DE 10 2005 045 090.
However, the common mode voltage uCM(t) can be used irrespective of the type of energy compensation (passive or active). It is only possible to limit the energy deviation of the energy stores by compensating currents in such a way that the level of these compensating currents does not result in unfavorable overdimensioning of the semiconductors by virtue of a simultaneous shift, as a result of a common mode voltage uCM(t), in the potentials of the converter output voltages u10(t), u20(t) and u30(t).
The additional valve branch current results in increased on-state losses and switching losses in the semiconductor switches which can be disconnected of the two- pole subsystems 10, 11 and 20 used. As a result, however, more favorable dimensioning of the energy stores of the subsystems 10, 11 and 20 used is achieved, i.e., this disadvantage is considered to be insignificant in comparison with the advantage (more favorable energy store dimensions).
When selecting amplitude, curve form (sinusoidal, trapezoidal, triangular, . . . ) and frequency of the common mode voltage uCM(t), in principle there are considerable degrees of freedom for the design. The following points play an important role in the dimensioning of the common mode voltage uCM(t):
    • Advantageously, the maximum rate of change
u CM ( t ) t | max
    • of the superimposed common mode voltage uCM(t) is selected such that it is not necessary for a plurality of energy stores 9 and 29, 30 of the subsystems 10, 11 and 20 used of a valve branch T1, . . . , T6 to be switched simultaneously in order to follow the predetermined setpoint value characteristic. As a result, the advantage of the lower motor insulation capacity as a result of low sudden voltage change levels in comparison with converters with a low number of stages would sometimes be given up again. In addition, low sudden voltage change levels have a positive effect on the level of the bearing and shaft currents and therefore increase the life of the drive.
    • The longer the potentials in the vicinity of the connections of the DC voltage busbar P0 or N0 of the polyphase converter shown in FIG. 1 are kept, the better the energy contents of the energy stores 9 and 29, 30 of the submodules 10, 11 and 20, respectively, which are in the switching state II can be matched to one another. For this reason, a trapezoidal curve characteristic of the common mode voltage uCM(t) with a pronounced plateau phase appears to be particularly advantageous, but not absolutely necessary.
    • The common mode voltage uCM(t) is to be dimensioned such that the resultant valve branch currents do not overshoot maximum values to be predefined.
    • The common mode voltage uCM(t) needs to be dimensioned such that the resultant voltage ripple ΔU in the energy stores 9 and 29, 30 of the subsystems 10, 11 and 20, respectively, used does not overshoot maximum values to be predefined.
When using the modulation of a common mode voltage uCM(t) according to the invention, it is necessary to ensure when using standard system motors that the maximum line-to-ground voltage uLE at the motor is not overshot in order not to damage the motor insulation. In the case of an ungrounded converter with DC isolation from the feed system by a feed-side transformer, it is generally the case that the potential of the neutral point of the machine winding is in the vicinity of the ground potential owing to the capacitive ratios. By virtue of the clocking of the converter, the potential ratios are shifted automatically in the converter. As a result, once the positive DC voltage busbar P0 is in the vicinity of the ground potential, and once the negative DC voltage busbar N0 is in the vicinity of the ground potential. In this case, it may arise at high common mode voltages uCM(t) that the total intermediate circuit voltage Ud is present at the machine terminals as line-to-ground voltage ULE. In the normal case, the following maximum condition therefore applies for the maximum value ûLE is of the line-to-ground voltage uLE:
u ^ LE = U d = 2 2 3 U M
where UM: rms value of the line-to-line motor voltage.
Even higher intermediate circuit voltages Ud and therefore higher values for ûLE are possible, but result in unfavorable design of the converter.
In the case of standard system motors which are designed for operation directly on the sinusoidal supply system, the maximum permissible value ûLE of the line-to-ground voltage ULE is lower by a factor of 2, however:
u ^ LEsystem = 2 3 U M
In order to solve this problem, it is advantageous to connect the fictitious mid-point of the intermediate circuit to the ground potential. This can take place with the aid of a resistor 40, by means of a capacitor 50 or by means of a parallel circuit comprising a resistor 40 and a capacitor 50, as shown in FIG. 12. As a result, the maximum voltage loading is halved and the maximum line-to-ground voltage at the machine terminals can thus be reduced to the maximum value ûLEsystem in the case of a sinusoidal system feed.
By means of this method according to the invention, the converter known from the conference proceedings relating to the ETG Conference 2002, which converter has a three-phase converter with distributed energy stores as shown in FIG. 1 on the system and load side, can be used as a drive converter which can be run up from standstill. In this application it is possible, even at low frequencies up to the DC operating mode of this converter, for the energy stores 9 and 29, 30 of the subsystems 10, 11 and 20 used to be dimensioned in optimum fashion.

Claims (8)

The invention claimed is:
1. A method for controlling a polyphase converter at a first output frequency, the converter comprising at least two phase modules, each phase module having an upper and a lower valve branch, with each of the upper and a lower valve branches each comprising at least two two-pole subsystems connected in series, with each subsystem comprising at least one energy store, the method comprising superimposing a common-mode voltage having a second frequency greater than the first output frequency on a setpoint value of a voltage of the upper and lower valve branches such that a sum of the voltages of the upper and lower valve branch of each phase module is equal to an intermediate circuit voltage of the polyphase converter and that a resulting voltage ripple of the at least one energy store of each subsystem does not exceed a predetermined maximum value.
2. The method of claim 1, wherein the common mode voltage is selected so that resulting valve branch current does not exceed a predetermined maximum value.
3. The method of claim 1, wherein an amplitude of the common mode voltage is inversely proportional to an increase in the output frequency of the polyphase converter.
4. The method of claim 1, wherein the common mode voltage is trapezoidal.
5. The method of claim 1, wherein the common mode voltage is sinusoidal.
6. The method of claim 1, wherein the common mode voltage is triangular.
7. A method for controlling a polyphase converter at a low output frequency, the converter comprising at least two phase modules, each phase module having an upper and a lower valve branch, with each of the upper and a lower valve branches each comprising at least two two-pole subsystems connected in series, the method comprising superimposing a common-mode voltage on a setpoint value of a voltage of the upper and lower valve branches such that a sum of the voltages of the upper and lower valve branch of each phase module is equal to an intermediate circuit voltage of the polyphase converter, wherein the common mode voltage is selected such that, for a maximum value for a line-to-ground voltage across terminals of a connected motor, the following condition is met:
u ^ LE U d 2 2 3 U M
where UM is an RMS value of a line-to-line motor voltage, ûLE is a maximum value for a line-to-ground voltage, and Ud is a total intermediate circuit voltage.
8. A method for controlling a polyphase converter at a low output frequency, the converter comprising at least two phase modules, each phase module having an upper and a lower valve branch, with each of the upper and a lower valve branches each comprising at least two two-pole subsystems connected in series, the method comprising superimposing a common-mode voltage on a setpoint value of a voltage of the upper and lower valve branches such that a sum of the voltages of the upper and lower valve branch of each phase module is equal to an intermediate circuit voltage of the polyphase converter, wherein the common mode voltage is selected such that, for a maximum value for a line-to-ground voltage across terminals of a motor designed for operating directly off a sinusoidal power supply system, the following condition is met:
u ^ LEsystem = 2 3 U M
where UM is an RMS value of a line-to-line motor voltage and ûLEsystem is a maximum line-to-ground voltage at machine terminals for a sinusoidal system feed.
US12/933,179 2008-03-19 2008-11-11 Method for controlling a polyphase converter with distributed energy stores at low output frequencies Active 2030-03-28 US8587248B2 (en)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
DE102008014898.9 2008-03-19
DE102008014898.9A DE102008014898B4 (en) 2008-03-19 2008-03-19 Method for controlling a multiphase power converter with distributed energy stores at low output frequencies
DE102008014898 2008-03-19
PCT/EP2008/065270 WO2009115141A1 (en) 2008-03-19 2008-11-11 Method for controlling a multi-phase power converter having distributed energy accumulator at low output frequencies

Publications (2)

Publication Number Publication Date
US20110018481A1 US20110018481A1 (en) 2011-01-27
US8587248B2 true US8587248B2 (en) 2013-11-19

Family

ID=40546054

Family Applications (1)

Application Number Title Priority Date Filing Date
US12/933,179 Active 2030-03-28 US8587248B2 (en) 2008-03-19 2008-11-11 Method for controlling a polyphase converter with distributed energy stores at low output frequencies

Country Status (8)

Country Link
US (1) US8587248B2 (en)
EP (1) EP2255434B1 (en)
CN (1) CN101971475B (en)
DE (1) DE102008014898B4 (en)
DK (1) DK2255434T3 (en)
ES (1) ES2664494T3 (en)
RU (1) RU2487458C2 (en)
WO (1) WO2009115141A1 (en)

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20120243282A1 (en) * 2009-12-01 2012-09-27 Siemens Aktiengesellschaft Converter for high voltages
US9698704B2 (en) 2013-01-31 2017-07-04 Siemens Aktiengesellschaft Modular high-frequency converter, and method for operating same
US20170279345A1 (en) * 2016-03-22 2017-09-28 Infineon Technologies Ag Active common mode cancellation

Families Citing this family (53)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE102005045091B4 (en) 2005-09-21 2007-08-30 Siemens Ag Control method for redundancy use in case of failure of a multiphase power converter with distributed energy storage
EP2443729B1 (en) 2009-06-15 2019-07-31 General Electric Technology GmbH Converter
CN102859861B (en) 2009-07-31 2016-01-20 阿尔斯通技术有限公司 Configurable hybrid converter circuit
DE102009043599B4 (en) * 2009-09-25 2013-10-24 Siemens Aktiengesellschaft Method of operating a modular multilevel inverter and multilevel inverter
CN102577077B (en) * 2009-10-15 2015-02-25 Abb瑞士有限公司 Method for operating an inverter circuit and device for performing the method
WO2011098117A1 (en) 2010-02-09 2011-08-18 Areva T&D Uk Limited Converter for high voltage dc dc transmission
WO2011113471A1 (en) 2010-03-15 2011-09-22 Areva T&D Uk Ltd Static var compensator with multilevel converter
WO2011127980A1 (en) * 2010-04-15 2011-10-20 Areva T&D Uk Limited Hybrid 2-level and multilevel hvdc converter
CA2802933C (en) 2010-06-18 2018-01-02 Alstom Technology Ltd Converter for hvdc transmission and reactive power compensation
EP2599199B1 (en) 2010-07-30 2018-02-28 General Electric Technology GmbH Hvdc converter comprising fullbridge cells for handling a dc side short circuit
US8878395B2 (en) 2010-08-04 2014-11-04 Unico, Inc. M2LC system coupled to a current source power supply
US8854843B2 (en) * 2010-08-24 2014-10-07 Alstom Technology Ltd. HVDC converter with neutral-point connected zero-sequence dump resistor
US8618698B2 (en) 2010-09-09 2013-12-31 Curtiss-Wright Electro-Mechanical Corporation System and method for controlling a M2LC system
DE102010041028A1 (en) * 2010-09-20 2012-03-22 Robert Bosch Gmbh Power supply network and method for charging at least one energy storage cell serving as energy storage for a DC voltage intermediate circuit in a power supply network
EP2619895A4 (en) 2010-09-21 2016-07-27 Benshaw Inc Two terminal multilevel converter
WO2012055435A1 (en) * 2010-10-27 2012-05-03 Alstom Grid Uk Limited Modular multilevel converter
EP2458725A1 (en) 2010-11-30 2012-05-30 ABB Research Ltd. Electric energy conversion system and method for operating same
CN102158064A (en) * 2011-01-26 2011-08-17 中国科学院等离子体物理研究所 Turn-off power semiconductor device valve and tandem topology structure thereof
CN102130619B (en) * 2011-03-21 2014-07-02 中国电力科学研究院 Voltage balancing control method for multi-level modular converter
DE102011006987A1 (en) 2011-04-07 2012-10-11 Siemens Aktiengesellschaft Modular power converter cabinet system
DE102011075576A1 (en) * 2011-05-10 2012-11-15 Siemens Aktiengesellschaft Converter arrangement
DE102011076039A1 (en) * 2011-05-18 2012-11-22 Siemens Aktiengesellschaft Converter arrangement
US9350250B2 (en) 2011-06-08 2016-05-24 Alstom Technology Ltd. High voltage DC/DC converter with cascaded resonant tanks
CN103597692B (en) * 2011-06-10 2016-08-17 Abb技术有限公司 Compensation system for medium-pressure or high pressure application
JP5518004B2 (en) * 2011-06-29 2014-06-11 三菱電機株式会社 Power converter
CN103891121B (en) * 2011-08-01 2016-11-23 阿尔斯通技术有限公司 DC-to-DC converter assembly
EP2748917B1 (en) 2011-08-24 2018-05-30 ABB Schweiz AG Bidirectional unisolated dc-dc converter based on cascaded cells
US20130091420A1 (en) * 2011-10-07 2013-04-11 David Shin Flyer Content Integration System
US9209693B2 (en) 2011-11-07 2015-12-08 Alstom Technology Ltd Control circuit for DC network to maintain zero net change in energy level
US9362848B2 (en) 2011-11-17 2016-06-07 Alstom Technology Ltd. Hybrid AC/DC converter for HVDC applications
KR101251166B1 (en) * 2011-12-12 2013-04-04 주식회사 효성 Unit and method for controlling module switching of power transform system
DE102012202173B4 (en) 2012-02-14 2013-08-29 Siemens Aktiengesellschaft Method for operating a multiphase, modular multilevel converter
IN2014MN01647A (en) 2012-03-01 2015-05-22 Alstom Technology Ltd
MX345133B (en) * 2012-03-09 2017-01-18 Benshaw Inc M2lc system and method for controlling same.
NL2010191C2 (en) 2012-07-23 2014-01-27 Univ Delft Tech Electrical power converter.
NL2009220C2 (en) * 2012-07-23 2014-01-27 Univ Delft Tech Electrical power converter.
EP2725700A1 (en) * 2012-10-23 2014-04-30 ABB Technology AG Controlling a modular multi-level converter
EP2858231B1 (en) * 2013-10-07 2019-09-11 General Electric Technology GmbH Voltage source converter
WO2015113642A1 (en) * 2014-02-03 2015-08-06 Abb Technology Ltd A multi-level power converter and a method for controlling a multi-level power converter
KR101711947B1 (en) * 2014-12-29 2017-03-03 주식회사 효성 Modular multilevel converter
CN104821736A (en) * 2015-05-15 2015-08-05 国家电网公司 Modularized multi-level converter with function of DC side short circuit protection
RU2584133C2 (en) * 2015-06-23 2016-05-20 Федеральное государственное бюджетное учреждение "Национальный медицинский исследовательский радиологический центр" Министерства здравоохранения Российской Федерации (ФГБУ "НМИРЦ" Минздрава России) Method of single-stage breast reconstruction in cancer using acellular dermal matrix and silicone implant
DE102015011004A1 (en) 2015-08-18 2017-02-23 Technische Universität Ilmenau Method for reducing the losses in a modular multipoint converter
DE102015116271A1 (en) * 2015-09-25 2017-03-30 Gottfried Wilhelm Leibniz Universität Hannover Method for operating a modular multilevel converter, modular multilevel converter and computer program
CN105759081B (en) * 2016-01-21 2020-02-21 中国电力科学研究院 Method for generating voltage waveform of aging test of lightning arrester of high-voltage direct-current transmission system
CN105515353B (en) * 2016-01-27 2018-06-19 东南大学 The four port electric power electric transformers based on mixed type module multi-level converter
CN105610336B (en) * 2016-01-27 2018-07-27 东南大学 MMC type multiport electric power electric transformer based on double capacitance modules
US10734912B2 (en) * 2016-08-24 2020-08-04 Beckhoff Automation Gmbh Stator device for a linear motor, linear drive system, and method for operating a stator device
CN106787648B (en) * 2016-11-30 2020-06-02 惠州Tcl移动通信有限公司 Method and system for protecting startup of mobile terminal
RU2689786C1 (en) * 2018-06-13 2019-05-29 Общество с ограниченной ответственностью "Транспортные прогрессивные технологии" Control method of multi-zone rectifier-inverter converter of single-phase alternating current
EP3772812A1 (en) * 2019-08-07 2021-02-10 ABB Schweiz AG Control of an icbt converter
TWI795052B (en) * 2021-10-28 2023-03-01 台達電子工業股份有限公司 Method of controlling power converter and power converter
CN116054620A (en) 2021-10-28 2023-05-02 台达电子工业股份有限公司 Control method of power converter and power converter

Citations (10)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
RU2119711C1 (en) 1996-03-11 1998-09-27 Акционерное общество открытого типа "Научно-исследовательский институт по передаче электроэнергии постоянным током высокого напряжения" Multiphase converter
US5831842A (en) * 1996-09-18 1998-11-03 President Of Okayama University Active common mode canceler
US5986909A (en) * 1998-05-21 1999-11-16 Robicon Corporation Multiphase power supply with plural series connected cells and failed cell bypass
DE10103031A1 (en) 2001-01-24 2002-07-25 Rainer Marquardt Current rectification circuit for voltage source inverters with separate energy stores replaces phase blocks with energy storing capacitors
EP1253706A1 (en) 2001-04-25 2002-10-30 ABB Schweiz AG Power electronic circuit and process to transfer active power
US7106025B1 (en) * 2005-02-28 2006-09-12 Rockwell Automation Technologies, Inc. Cancellation of dead time effects for reducing common mode voltages
US20070026872A1 (en) 2005-07-29 2007-02-01 Siemens Aktiengesellschaft Method for determining a relative position of a mobile unit by comparing scans of an environment and mobile unit
DE102005041087A1 (en) 2005-08-30 2007-03-01 Siemens Ag Static inverter circuit has interconnect points formed between semiconductor switches for connection terminals of two-pole subsystem and connection to reference potential connection of electronics
WO2007033852A2 (en) 2005-09-21 2007-03-29 Siemens Aktiengesellschaft Method for controlling a multiphase power converter having distributed energy stores
WO2007139800A2 (en) 2006-05-22 2007-12-06 Regents Of The University Of Minnesota Carrier-based pulse-width modulation (pwm) control for matrix converters

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP3517081B2 (en) * 1997-05-22 2004-04-05 株式会社東芝 Multi-level nonvolatile semiconductor memory device
US7016025B1 (en) * 1999-06-24 2006-03-21 Asml Holding N.V. Method and apparatus for characterization of optical systems

Patent Citations (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
RU2119711C1 (en) 1996-03-11 1998-09-27 Акционерное общество открытого типа "Научно-исследовательский институт по передаче электроэнергии постоянным током высокого напряжения" Multiphase converter
US5831842A (en) * 1996-09-18 1998-11-03 President Of Okayama University Active common mode canceler
US5986909A (en) * 1998-05-21 1999-11-16 Robicon Corporation Multiphase power supply with plural series connected cells and failed cell bypass
DE10103031A1 (en) 2001-01-24 2002-07-25 Rainer Marquardt Current rectification circuit for voltage source inverters with separate energy stores replaces phase blocks with energy storing capacitors
EP1253706A1 (en) 2001-04-25 2002-10-30 ABB Schweiz AG Power electronic circuit and process to transfer active power
US7106025B1 (en) * 2005-02-28 2006-09-12 Rockwell Automation Technologies, Inc. Cancellation of dead time effects for reducing common mode voltages
US20070026872A1 (en) 2005-07-29 2007-02-01 Siemens Aktiengesellschaft Method for determining a relative position of a mobile unit by comparing scans of an environment and mobile unit
DE102005041087A1 (en) 2005-08-30 2007-03-01 Siemens Ag Static inverter circuit has interconnect points formed between semiconductor switches for connection terminals of two-pole subsystem and connection to reference potential connection of electronics
WO2007033852A2 (en) 2005-09-21 2007-03-29 Siemens Aktiengesellschaft Method for controlling a multiphase power converter having distributed energy stores
DE102005045090A1 (en) 2005-09-21 2007-04-05 Siemens Ag Method for controlling a multiphase power converter with distributed energy storage
US20080310205A1 (en) 2005-09-21 2008-12-18 Siemens Aktiengesellschaft Method for Controlling a Polyphase Converter With Distributed Energy Stores
WO2007139800A2 (en) 2006-05-22 2007-12-06 Regents Of The University Of Minnesota Carrier-based pulse-width modulation (pwm) control for matrix converters
US7869236B2 (en) 2006-05-22 2011-01-11 Regents Of The University Of Minnesota Carrier-based pulse-width modulation (PWM) control for matrix converters

Non-Patent Citations (5)

* Cited by examiner, † Cited by third party
Title
A. Lesnicar, R. Marquardt IEEE Bologna PowerTech Conference, Jun. 23-26, 2003, Bologna, Italy.
K.A.Corzine, S.Lu Electric Ship Technologies Symposium, 2005 IEEE Philadephia USA, Jul. 25-27, 2005, Seiten 355-362; Others; 2005; US.
M. Veenstra, Prof. A. Rufer Conference Record of the 2003 IEEE Industry Applications Conference; IAS Annual Meeting, Salt Lake City Oct. 12-16, 2003; Others; 2003; US.
R. Marquardt, A. Lesnicar, J. HildingeETG-Tagung 2002; Book; 2002.
Shuai Lu, Keith A.Corzine Power Electronics and Motion Control Conference, IPMC'06, Jan. 8, 2006, Seiten 1-5; Others; 2006.

Cited By (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20120243282A1 (en) * 2009-12-01 2012-09-27 Siemens Aktiengesellschaft Converter for high voltages
US9130477B2 (en) * 2009-12-01 2015-09-08 Siemens Aktiengesellschaft High voltage converter for limiting short-circuit currents
US9698704B2 (en) 2013-01-31 2017-07-04 Siemens Aktiengesellschaft Modular high-frequency converter, and method for operating same
US20170279345A1 (en) * 2016-03-22 2017-09-28 Infineon Technologies Ag Active common mode cancellation
US9800133B2 (en) * 2016-03-22 2017-10-24 Infineon Technologies Ag Active common mode cancellation

Also Published As

Publication number Publication date
CN101971475A (en) 2011-02-09
RU2487458C2 (en) 2013-07-10
DE102008014898A1 (en) 2009-09-24
WO2009115141A1 (en) 2009-09-24
EP2255434A1 (en) 2010-12-01
RU2010142502A (en) 2012-04-27
ES2664494T3 (en) 2018-04-19
DE102008014898B4 (en) 2018-09-27
US20110018481A1 (en) 2011-01-27
CN101971475B (en) 2015-04-29
DK2255434T3 (en) 2018-03-12
EP2255434B1 (en) 2018-01-03

Similar Documents

Publication Publication Date Title
US8587248B2 (en) Method for controlling a polyphase converter with distributed energy stores at low output frequencies
RU2670195C2 (en) Converter, electric multiphase system and method of their implementation
Korn et al. Low output frequency operation of the modular multi-level converter
EP1953907B1 (en) Systems and methods for improved motor drive power factor control
EP1882297B1 (en) Variable-frequency drive with regeneration capability
US8233300B2 (en) Device for converting an electric current
US9036379B2 (en) Power converter based on H-bridges
US6977449B2 (en) Frequency converter and drive for electric motor
US20080094019A1 (en) Bidirectional buck-boost power converters
US10110110B2 (en) Power conversion device
EP1670130A2 (en) Power conversion system and method
RU2649888C2 (en) Assembly for compensating reactive power and active power in a high-voltage network
US9899917B2 (en) Method for producing an output voltage and assembly for performing the method
EP2421129A2 (en) Power converter system and method
EP3046246B1 (en) Multilevel active rectifiers
US20230361680A1 (en) Power conversion device
US20230035598A1 (en) Power conversion device
US10811990B1 (en) Multi-segment and nonlinear droop control for parallel operating active front end power converters
US11677335B2 (en) Method for operating a power converter
Ounejjar et al. Multilevel hysteresis controller of the novel seven-level packed U cells converter
US20210013795A1 (en) Dc-link charging arrangement and method for charging a dc-link capacitor
WO2023214462A1 (en) Power conversion device
GB2620578A (en) A voltage converter and method of converting voltage
KR20090019281A (en) Motor control device

Legal Events

Date Code Title Description
AS Assignment

Owner name: SIEMENS AKTIENGESELLSCHAFT, GERMANY

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:HILLER, MARC, DR.;REEL/FRAME:025004/0942

Effective date: 20100823

FEPP Fee payment procedure

Free format text: PAYOR NUMBER ASSIGNED (ORIGINAL EVENT CODE: ASPN); ENTITY STATUS OF PATENT OWNER: LARGE ENTITY

STCF Information on status: patent grant

Free format text: PATENTED CASE

FPAY Fee payment

Year of fee payment: 4

MAFP Maintenance fee payment

Free format text: PAYMENT OF MAINTENANCE FEE, 8TH YEAR, LARGE ENTITY (ORIGINAL EVENT CODE: M1552); ENTITY STATUS OF PATENT OWNER: LARGE ENTITY

Year of fee payment: 8

AS Assignment

Owner name: INNOMOTICS GMBH, GERMANY

Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:SIEMENS AKTIENGESELLSCHAFT;REEL/FRAME:065612/0733

Effective date: 20231107