|Publication number||USRE31749 E|
|Application number||US 06/168,777|
|Publication date||Nov 27, 1984|
|Filing date||Jul 11, 1980|
|Priority date||Sep 3, 1975|
|Also published as||DE2639598A1, DE2639598B2, US4100502|
|Publication number||06168777, 168777, US RE31749 E, US RE31749E, US-E-RE31749, USRE31749 E, USRE31749E|
|Original Assignee||Hitachi, Ltd.|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (17), Non-Patent Citations (4), Referenced by (36), Classifications (22)|
|External Links: USPTO, USPTO Assignment, Espacenet|
1. FIELD OF THE INVENTION
This invention relates to an amplifier circuit and more particularly to a complementary metal-insulator-semiconductor (C-MIS) amplifier circuit comprising a p-channel metal-insulator-semiconductor field effect transistor (referred to as MIS FET or simply as FET, hereinbelow) and an n-channel MIS FET.
2. DESCRIPTION OF THE PRIOR ART
Conventionally, such a circuit as shown in FIG. 4 has been known as a crystal oscillator circuit used in an electronic wristwatch from U.S. Pat. No. 3,676,801 issued to F. H. Musa, an American publication, "RCA COS/MOS Integrated Circuits Manual" by RCA Corporation, pages 192 to 205, 1972, etc. The circuit of FIG. 4 basically comprises a C-MIS inverter circuit including an n-channel FET Mn and a p-channel FET Mp, and a positive feedback circuit or a regenerative feedback loop connected between the input and output terminals of the inverter circuit and including a crystal oscillator X and capacitors CD and CG. A resistor RD provided at the output of the amplifier circuit serves to stabilize the oscillation frequency.
Such a circuit as described above, however, has a problem in that the power consumption becomes large. This can be described as follows.
When the complementary inverter amplifier circuit constituting the main part of the oscillator circuit is driven with a complementary digital input signal without other components, the period during which both complementary FETs are turned on is very short and the power consumption due to the dc current passing through the two FETs caused little problem since the complementary FETs operate in a push-pull manner. When a linear (e.g., a sinusoidal) signal as shown in FIG. 5 is applied to the input terminal, however, the period during which the two FETs operate in the transfer region or in the neighborhood of the switching point (the region between the threshold voltages Vthn and Vthp of the FETs Mn and Mp, i.e., the hatched region Y in FIG. 5) becomes long and the power dissipation increases.
An object of this invention is, therefore, to provide a complementary inverter amplifier circuit of low power consumption.
Another object of this invention is to provide a complementary inverter amplifier circuit accompanied with no loss current through MIS FETs which occurs due to the threshold voltage of the MIS devices in the case of amplifying a linear input.
A further object of this invention is to provide a complementary MIS inverter amplifier circuit serving as a linear amplifier means in an oscillator circuit and having an arrangement of preventing a loss or invalid current through the inverter in supplying an oscillation output to a waveform shaping MIS inverter of the following stage.
Another object of this invention is to provide a complementary MIS inverter amplifier circuit capable of monolithic integration and adapted for use in the circuit requiring low power consumption such as a micropower crystal-controlled oscillator in an electronic timepiece such as an electronic wristwatch.
Another object of this invention is to provide a complementary MIS inverter amplifier circuit having a complementary MIS inverter biased to serve as a class B push-pull amplifier.
According to one aspect of this invention, there is provided a complementary inverter amplifier comprising a complementary inverter including a first FET of a first conductivity type connected to a first source potential and a second FET of a second conductivity type connected to a second source potential, an input being applied commonly to the gates of the first and the second FETs, the amplifier comprising a first and a second load resistors connected in series between the first and the second FETs, bias resistors connected between the gate and the drain of the first and the second FETs, an input being supplied to the gates of the FETs through respective capacitive elements and an output being derived from the interconnection point of the first and the second load resistors or from the drains of the first and the second FETs thereby providing a class B push-pull amplifier function.
These and other objects, features and advantages of the present invention will become more apparent from the following detailed description of the invention when taken in conjunction with the accompanying drawings.
FIG. 1 is a circuit diagram of a complementary inverter amplifier according to an embodiment of this invention.
FIG. 2 shows voltage transfer characteristic curves for illustrating the operation of the circuit of FIG. 1.
FIG. 3 is a circuit diagram of an oscillator circuit including an embodiment of the amplifier circuit according to this invention.
FIG. 4 is a circuit diagram of a conventional oscillator circuit.
FIG. 5 is a graph for illustrating the reason for allowing a loss through-current in the conventional circuit of FIG. 4.
FIG. 6 is a circuit diagram of a complementary MIS FET amplifier according to another embodiment of this invention.
FIG. 7 is a circuit diagram illustrating a modification of FIG. 1.
FIG. 8 is a sectional view of an MIS capacitor illustrating an ac coupling capacitor used in the present amplifier.
Throughout the drawings, the same reference letters or characters indicate the same parts.
FIG. 1 shows a complementary inverter amplifier according to an embodiment of this invention, in which the circuit is arranged to operate as a class B push-pull amplifier by appropriately selecting the operational bias point of each of FETs Mn and Mp and to achieve reduction of the power consumption.
An n-channel enhancement mode FET Mn (grounded source) connected to a potential source -VDD and a p-channel enhancement mode FET Mp (grounded source) connected to a different potential source VSS, ground in this example are connected in a series fashion to form a complementary inverter. Here, between the complementary FETs Mn and Mp, two load resistors RL1 and RL2 of equivalent resistance are connected in series. Further, biasing resistors RF1 and RF2 are connected for the FETs Mn and Mp between the gate and the drain thereof, respectively. The gate of the FETs Mn and Mp are supplied with a common input signal Vin through respective capacitors C1 and C2 for ac coupling. An output Vout of the circuit is derived from the interconnection point of the load resistors RL1 and RL2. Letters C, D, A and B denote various points shown in the figure, i.e., the gates and drains of the FETs. The purposes of this invention can be achieved by the above structure as will be apparent from the following description of the operation of the circuit.
In FIG. 2, the ordinate represents the output voltage of the FET and the abscissa the input voltage. The solid curve represents the relation between the voltages c and a at the gate C and the drain A of the FET Mn, i.e., the voltage transfer characteristic curve of the FET Mn, while the broken curve represents the relation between the voltages d and b at the gate D and the drain B of the FET Mp, i.e., the voltage transfer characteristic curve of the FET Mp. The biasing resistors RF1 and RF2 serve to equalize the dc levels of the gate and the drain voltages of the FETs Mn and Mp, respectively. The lower the biasing resistance, the better stabilized is the biasing voltage, while the higher the biasing resistance, the higher held is the amplification factor. Considering these properties, the resistances of the biasing resistors RF1 and RF2 may be selected as approximately 10 megohms and may be formed of diffused resistors, polycrystalline Si resistors or on-resistances between the source and the drain of FETs. In detail, the biasing resistors RF1 and RF2 may be formed of on-resistances of a transmission gate of high resistance in the range of several to several tens megohms, which is formed of complementary MIS FETs to enable a monolithic integrated circuit form. The MIS FETs of the transmission gate are connected in parallel between the input and output terminals of the amplifier circuit. Here, the gate of the p-channel MIS FET is connected to the power supply voltage -VDD and the gate of the n-channel MIS FET to ground. Further, the higher is selected the resistance of the load resistors RL1 and RL2 compared to the on-resistance of the respective FETs, the steeper slope shows the voltage transfer characteristic curve and the closer the potential differential between the drain and the source (or gate-to-source) of each of the FETS Mn and Mp approaches the respective threshold voltage, the closer the biasing voltage approaches the threshold voltage, reducing the power consumption. Since the dc component in the input voltage Vin is blocked by the ac coupling or dc blocking capacitors C1 and C2, the biasing points of the FETs Mn and Mp are determined separately and independently of the input signal level.
When an input signal Vin, e.g., a linear signal such as a sinusoidal wave by the oscillating operation, is applied, the voltages at the gate points as shown by C and D in FIG. 1, of the FETs Mn and Mp receiving the input signal through the respective capacitors C1 and C2 are represented by the curves c and d in FIG. 2 respectively. Then, the FETS Mn and Mp having operational points as described above provide amplified outputs a and b at the respective drain points as shown by A and B in FIG. 1. A total output may take the combination of these signals a and b.
Therefore, in the former half of the cycle the FET Mp is turned on to generate a signal at the point B and in the latter half the FET Mn is turned on the generate a signal at the point A. Namely, the output signal in the whole cycle has a waveform as shown by the hatched areas in FIG. 2. In this way, the two FETs of the complementary type take charge of the amplification in respective half cycles to totally perform the operation of a class B push-pull amplifier.
According to the above structure, the present circuit performs the class B push-pull operation and hence the period during which the two FETS are both turned on becomes short. Thus, the period of allowing a through-current to pass becomes short and the power consumption is greatly reduced.
The above analysis holds perfectly when the circuit operates ideally. In practical use, however, there remains a small possibility of momentarily allowing the turning-on of both FETs, i.e., the flow of a through-current, from the relation to the operational speed of the FETs even in the above circuit. In such a case, however, the through-current is limited in magnitude by the load resistors RL1 and RL2 and is almost negligible. Therefore, a complementary inverter amplifier of low power comsumption is provided.
The present invention is not limited to the above embodiment and various alternations and modifications would be possible.
For example, the output of the above complementary amplifier is derived from the interconnection of the load resistors RL1 and RL2 connected in series between the conduction paths of the two FETS Mn and Mp in the above embodiment, but it may be replaced by those derived from the respective drains of the two FETs according to the use or purposes. An example of such a case is shown in FIG. 3 in which the inverter amplifier is used in an oscillator circuit.
FIG. 3 shows a crystal-controlled oscillator circuit for use in an electronic wristwatch. The complementary inverter circuit according to an embodiment of this invention is used as the amplifier means and a positive feed-back circuit including a crystal oscillator X and capacitors CD and CG is connected between the input and output terminals of the amplifier. Generally, an output signal Vout of this oscillator circuit is applied to a frequency divider circuit through a waveform shaping inverter which is also called a logic circuit. Here, the following problem arises.
Since the load resistors RL1 and RL2 are provided in the complementary inverter of the oscillator circuit, the output Vout of the oscillator resembles a sinusoidal wave. Therefore, if such a sinusoidal wave is directly applied to an inverter of the next circuit stage, a through-current is allowed to pass through the inverter for a long period to increase the power consumption.
Therefore, in the circuit of FIG. 3, the voltages VA and VB at the respective drains of the FETs Mn and Mp are derived as the outputs of the complementary amplifier and are applied to the gates of an n-channel FET Mnl and a p-channel FET Mpl of a complementary inverter, respectively, whose drain electrodes are connected in common to constitute an output terminal VE. The source electrodes of the FETs Mnl and Mpl are connected to the operating potential sources -VDD and VSS respectively. The output of the complementary inverter is then supplied to a frequency divider G through a waveform shaping inverter INV. In this arrangement, two amplified output signals VA and VB are supplied to the gates of the corresponding FETs Mnl and Mpl of the complementary inverter in the next circuit stage. Then, since no load resistor is used in this complementary inverter, a square wave is provided at an output terminal VE. Hence, the through-current in the waveform shaping inverter INV is minimized and an oscillator circuit of low power operation is provided.
FIG. 6 shows a complementary MIS amplifier circuit according to another embodiment of this invention, in which an n-channel MIS FET MN and a p-channel MIS FET MP are connected in series between two operating voltage terminals, one at -VDD and the other at a reference level, e.g., ground. A resistor RL is connected between the drains of the MIS FETs MN and MP to suitably limit a current passing through the conduction paths of these FETs. A biasing resistor RF is coupled between an input terminal IN and an output terminal OUT of the amplifier. The bias point for the MIS FET MP which is set at a potential in the neighborhood of the threshold voltage Vth of the MIS FET Mp is shown by way of example. The gates of the complementary MIS FETs MN and MP are commonly in ac sense connected to the input terminal IN. Output deriving points and linear biasing of the circuit may be selected in various manners according to the need of the designer, for example, as shown in FIG. 1 or FIG. 3.
In this circuit, since the conduction current limiting resistor RL is provided in the drain side of the amplifier FET but not in the source side, a feed-back loop as in the latter case is not formed, so that the amplifier circuit can achieve low power consumption without substantially lowering its amplification, and also, the dispersion or variation in the amplification of the amplifier due to the manufacturing dispersion of the resistance of the resistor RL becomes small. Further, since the MIS FET MP is biased to operate as class B amplifier, low power dissipation is successfully achieved.
FIG. 7 illustrates a modified circuit of FIG. 6 but similar to FIG. 1, in which no ac coupling capacitor is provided between the input terminal IN and the MIS FET MP and instead, this transistor is biased directly by the biasing resistor RF2. Consequently, no attenuation of an ac input signal due to the ac coupling capacitor, which will be applied to the MIS FET MP will occur. Also, since the number of circuit components is reduced compared with the circuit of FIG. 1, it is advantageous to produce the circuit in an IC chip. The output terminal OUT may be provided at the drain of the MIS FET MN.
Capacitors for ac coupling capacitors C1 and C2 may be integrated in an MIS integrated circuit. Namely, an MIS capacitor for the capacitor C1 or C2 may be formed as shown in FIG. 8 using a so-called silicon-gate MOS process by which other transistors are fabricated in the same chip. In the MIS capacitive structure, a p-type semiconductor well region 2 is formed in an n-type semiconductor substrate 1 grounded to constitute one electrode of the capacitor. A silicon dioxide layer 3 is formed over the surface of the semiconductor substrate. On the surface of the well region 2 a thin silicon dioxide film 4 is formed, on which a polycrystalline silicon layer 5 is provided to constitute the other electrode of the capacitor. The electrode layer 5 is led to a terminal E1. A p+ -type diffused region (not shown) is formed in the p-type well region 2 from which another terminal E2 is formed through the silicon dioxide layer 3. Thus, the capacitor is formed of an MOS capacitance established between the p-type well region and the polycrystalline silicon layer 5, and is isolated from ground. The leadout p+ -type region is diffused in the well region 2 simultaneously with the step of diffusing source and drain regions for other MIS elements.
It will be apparent that in the amplifier circuits described above, the polarities of the FETs may be reversed with the inversion of the polarity of the power source potentials.
Further, any circuits and/or circuit elements may be added to the basic circuit structures of the above embodiments for operating the circuit more effectively.
This invention can be widely utilized as an amplifier circuit of low power consumption adapted for monolithic integration.
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|U.S. Classification||330/264, 331/116.0FE, 330/267, 968/823, 327/109|
|International Classification||H03F3/347, H01L27/04, H03F3/34, H03F3/30, H03F3/20, H03F3/213, H03K19/0948, H03F3/345, H01L21/822, G04F5/06, H03B5/36|
|Cooperative Classification||H03F3/3028, H03K19/0948, G04F5/06|
|European Classification||H03K19/0948, G04F5/06, H03F3/30B6B|