|Publication number||USRE35644 E|
|Application number||US 07/883,561|
|Publication date||Oct 28, 1997|
|Filing date||May 15, 1992|
|Priority date||Mar 30, 1988|
|Also published as||US4939446|
|Publication number||07883561, 883561, US RE35644 E, US RE35644E, US-E-RE35644, USRE35644 E, USRE35644E|
|Inventors||Wesley A. Rogers|
|Original Assignee||Electronic Development Inc.|
|Export Citation||BiBTeX, EndNote, RefMan|
|Patent Citations (10), Non-Patent Citations (9), Referenced by (2), Classifications (6), Legal Events (1)|
|External Links: USPTO, USPTO Assignment, Espacenet|
This invention relates to method and apparatus for testing the susceptibility of devices, such as circuitry, to electromagnetic interference (EMI).
Analog and digital electronic circuitry and attendant wiring may encounter serious operating difficulty in the presence of strong electromagnetic fields. Such fields are generally referred to as Electromagnetic Interference (EMI) fields. The circuits and attendant wiring may be shielded and filtered to provide some immunity to large EMI fields, however, it is not possible or practical to design the circuitry and attendant wiring so as to ensure immunity to EMI fields. Method and apparatus, therefore, are required to test the susceptibility of the circuits and attendant wiring to EMI fields.
EMI testing is typically performed in shielded enclosures, known as "screen rooms", which provide an electromagnetic environment wherein only controlled EMI fields are present. Apparatus typically used inside the screen room includes current probes attached to a harness wire and a transmitter which sends the signals detected by the probes to a receiver outside the screen room, where the effects of the EMI fields on the circuit are determined.
To ensure the integrity of the screen room and the results of the EMI tests, any voltage measuring apparatus within the screen room should minimally perturb the controlled EMI fields and should be energized by a signal from the device under test only. For example, any test apparatus which might reradiate EMI fields impinging on the device under test or might otherwise inject any noise into the device under test must be avoided.
Probes suitable for monitoring current during EMI tests are commercially available. The Ailtech model number 91197-11 is one such device. Voltage probes are available, however, none are adequate to monitor voltages during EMI radiated susceptibility testing. Existing wire probes act as an antenna in the screen room, picking up energy from the controlled EMI fields. The induced energy on the probes may be injected into the device under test at the point of monitoring, where it can degrade performance. Existing wire probes, therefore, may cause an erroneous indication of susceptibility to EMI fields.
The lack of suitable wire voltage probes for use in EMI testing has resulted in the promulgation of test procedures, in certain industries, specifying that wired instrumentation, such as voltage probes, not be used.
It is an object of the present invention to provide a voltage probe and transmitter for monitoring the effect of EMI on a device under test.
It is a further object of the present invention to provide a voltage probe which does not affect the device under test, or the test results, in the presence of EMI fields.
It is a further object of the present invention to provide an electromagnetically transparent voltage probe.
It is a further object of the present invention to provide a method for measuring the effect of EMI fields on a device under test, without effecting the device under test or the test results.
In accordance with this invention an electromagnetically transparent voltage probe comprises electrically overdamped input conductors and a hybrid electrical/optical data transmitter having a high impedance input port connected to one end of the input conductors. The other end of the input conductors is connected to a device under test by short conducting clips. The clips' insulation is surface coated, with any bright, metallic, reflecting material such as a silver paint or foil to shield the clip contact from impinging EMI fields, thereby preventing the injection of signals into the device under test by the clip. The transmitter has an optical output port that is connected to a receiver by way of an EMI immune optical fiber, where the effects of controlled EMI fields on the device under test are monitored.
The input conductors may comprise a thread core impregnated with fine conducting particles and an insulating sheath. The overdamped conductors have a high distributed resistance so that they will not ring or tune at the frequencies of interest and, therefore, will not pick up energy from the EMI fields. As a result, the voltage probe transmission link may be used to monitor voltages of a device under test in the presence of a strong EMI field.
FIG. 1 is an illustration of the voltage probe, in accordance with the present invention, as used in a screen room in conjunction with a transmitter and receiver.
FIG. 2 is a schematic representation of a hybrid electrical/optical analog transmitter in accordance with a first embodiment of the present invention.
FIG. 3 is a schematic representation of a hybrid electrical/optical differential digital transmitter in accordance with a second embodiment of the present invention.
The application of a voltage transmission link in the EMI testing of electronic devices in a screen room 101, in accordance with the invention, is illustrated in FIG. 1 of the drawings. The device under test (DUT) 105 may be a component with attendant wiring resting on a test table 104 or may be a product, e.g., electronic circuit boards with attendant wiring harness and cables, which is installed in a large structure, such as an automobile. The DUT 105, is inside an EMI screen room 101 which provides a controlled electromagnetic environment, in which the antennae 102 and 103 generate EMI fields of known characteristics. While the screen room provides a convenient test environment, it is also possible to perform EMI testing in accordance with the invention without the benefit of a screen room.
The sources for driving the antennae 102 and 103 are not shown in the drawing and are usually located outside the screen room 101. There are controls for selectively turning the sources on and off and for setting the level of power and the frequencies of the signals applied to the antennae 102 and 103.
The transmitter 106 and the connectors 107, 108 and 109 provide the capability to monitor points of interest in a DUT 105 having either differential or single ended outputs. If the output is a differential signal, the conductors 107 and 108 are connected to the signal points of interest and the conductor 109 is connected to ground in the DUT 105. If the output is single ended, the conductor 107 is connected to that point of interest and the conductor 109 is connected to ground in the DUT 105, while the conductor 108 is not connected.
The connection to the points of interest in the DUT 105 is made by short conductive clips 120. Typically, the clips should have a length less than or equal to one centimeter to prevent the EMI electric field from coupling onto the clip and subsequent injection of energy into DUT 105. A one centimeter long clip will half-wavelength tune to 15 Ghz. This is effectively outside the uppermost frequency of interest--12.4 Ghz. To allow the convenience of operation with longer clips and to extend the frequency range of operation to higher frequencies, the clips' insulation is coated with a conductive paint or foil, open at both ends, that effectively shields the clip from EMI. The coating also prevents the clip from reradiating EMI that has coupled onto the DUT 105. One such clip is a product number KLEPS3STO.64 marketed by Hirshmann Inc. of America. The conductors 107, 108 and 109 are connected to the input ports A, B and G, respectively, of the transmitter 106 by BNC connectors, such as those marketed by Amphenol under product number 31-1002.
The conductors 107, 108 and 109, in accordance with the invention, are of construction that renders them transparent to impinging electromagnetic fields, so that they do not pick up any energy from electromagnetic fields. They may comprise a continuous monofilament core of plastic which is impregnated with fine conductive particles, such as carbon and covered with a plastic insulating sheath. A conductor material with the above described characteristics is marketed by The Polymer Corporation of Reading, Pa. under the tradename FLUOROSINTŪ 719. It comprises a carbon/fluoropolymer core 0.030 inches in diameter enclosed by a transparent nylon insulating cover with an outer diameter of 0.040 inches and has resistance per length of cable within the range of 20,000 to 30,000 ohms per foot.
These conductors, therefore, have a uniformly distributed resistance, capacitance and inductance which causes them to be electrically overdamped and transparent to EMI fields. The conductors do not ring or tune at frequencies of interest in EMI testing and, therefore, will not pick up RF energy from EMI fields.
Referring to FIGS. 2 and 3 of the drawings, analog and digital embodiments of the data transmitter 106 are illustrated. In describing both embodiments, the A and B input ports comprise a FET input operational amplifier 202 and 204, such as Motorola's product number LF357BJ. The conductors 107 and 108 are connected through a BNC connector to the non-inverting terminal of the respective operational amplifiers 202 and 204. Each operational amplifier is configured in the voltage follower mode, with the output fed back to the inverting terminal, so that the input impedance is multiplied by the open loop gain of the operational amplifier. A very high input impedance is thus obtained, thereby limiting current in the conductors 107 and 108 to less than five nanoamperes.
The output of the operational amplifier 202 goes to the inverting terminal of differential amplifier 206 through a series resistor 208. The output of the operational amplifier 204 goes to the non-inverting terminal of the differential amplifier 206 through a series resistor 210. The differential amplifier 206 provides common mode rejection for differential signals. The common mode signal will move in phase at the non-inverting inputs at operational amplifiers 202 and 204. Since these signals have equal paths to the inputs of the differential amplifier 206, they will be in phase there as well. Since the differential amplifier 206 only amplifies the difference in signals at its inputs, the common mode signals are rejected.
The resistor 214 and adjustable resistor 216 bias the output of the differential amplifier 206 for linear output voltage swings across the light emitting diode (LED) 226. Resistor 212 provides a feedback path for the output of the differential amplifier 206 to its inverting input. Amplifier 206 is connected for unitary gain in order to avoid over driving the LED 226 with large (10Vpp) analog input signals.
Referring to FIG. 2 of the drawings, the remaining portion of the analog transmission circuit will be described. The output of the differential amplifier 206 is input to the base of transistor 224 through a series resistor 218. The resistors 218, 220 and 222 bias the transistor 224 for linear operation. The emitter of transistor 224 is connected to the anode of the LED 226. The cathode of the LED 226 is connected to ground in series with a current limiting resistor 228. The analog optical output of the LED 226 is applied to a fiber optic cable 111 by way of an optical port 110.
The LED 226 is activated when transistor 224 is driven by the output of the differential amplifier 206 in response to the presence of differential signals at input ports A and B. The analog transmission circuit of FIG. 2 is capable of transmitting non-square wave signals from DC to 1 MHz. For square waves, the accurate circuit response is up to 100 kHz. A center tapped battery operated power supply is employed as shown in FIG. 2.
Referring to FIG. 3 of the drawings, the input operational amplifiers 202 and 204 and the differential amplifier 206 for common mode rejection are the same as in the analog transmitter of FIG. 2. The remaining portion of the digital transmission circuit will now be described. The output of the differential amplifier 206 is connected to the inverting input of a wideband high gain amplifier 330 through series resistor 333. The non-inverting input of amplifier 330 is grounded and its output is fed back through resistor 332 to the inverting input. Amplifier 330 provides voltage gain to the differential signal.
The amplified signal is applied to a pulse restoration circuit which comprises a potentiometer 334, capacitor 336 and exclusive NOR gate 338. The voltage output of the amplifier 330 is a one volt signal that depends on the differential input signals and is offset by a three volt DC level. The potentiometer 334 is adjusted to reduce the offset to a level where the one volt signal will cross the input threshold of gate 338 to properly trigger the gate 338. The output of amplifier 206 is reduced to 1 volt at 20 MHz due to probe attenuation at frequencies above 1 MHz. The input to amplifier 330 is approximately 10 mV at 10 MHz. A high gain amplifier is therefore required for the digital path. As a result, the gate 338 is triggered to output a fast rise time four volt signal when there is a differential digital signal at the input ports A and B, so that the LED 344 will output the differential signal on the optical cable 111. The diode 340 is a high speed diode that improves the rise time of the output signal. The gate 338 is not triggered when there is a common mode input at ports A and B, so that current flows from resistor 342 through the forward biased diode 340, thereby abutting the LED 344 off.
The digital transmission circuit of FIG. 3 is capable of transmitting digital signals with data rates in the range of DC to 20 MHz. As mentioned above, the analog signal path of FIG. 1 may be used for square waves with frequencies less than 100 kHz. Both the analog and digital circuits generally transmit a linear reproduction of the original waveform, but this is not necessary, since EMI typically manifests itself in much higher frequencies which tend to modulate the waveforms. It is only necessary, therefore, to measure changes in the signals under test.
The transmission circuits of FIGS. 2 and 3 may also receive single ended signals from a DUT 105 and transmit them to the receiver 116. This is accomplished by connecting the B input of each transmitter to ground, so that the non-inverting input of the operational amplifiers 204 is grounded. A switch may be provided . .an.!. .Iadd.on .Iaddend.the front panel of the transmitter 106 to switch between single ended and differential signals.
The circuits of the transmitter 106 should be packaged in an enclosure that shields against EMI fields as high as 300 volts per meter. Also, the transmitter is powered by an internal battery within the enclosure, thereby avoiding external power leads and the necessity of providing sufficient EMI filtering.
Referring back to FIG. 1 of the drawings, the optical port 110 of the transmitter 106 is coupled to the receiver 116 by the fiber optic cable 111. The connectors at the ports 110 and 114 are optical and the feed through device 112 passes the cable 111 from the screen room 101 without transfer of EMI fields to or from the screen room. The receiver 116 is connected to a recorder, e.g. an oscilloscope 119, by a shielded electrical cable 117. The receiver 116 may be any commercially available receiver capable of handling the bandwidth of the output signals from the transmitter 106. The receiver 116 and transmitter 106 should be housed in a shielded enclosure that provides EMI immunity to fields as large as 300 volts per meter.
A DUT 105 may be tested for susceptibility to EMI fields in a screen room 101, as illustrated in FIG. 1 of the drawings, as follows. Signals from the DUT 105 are transmitter to the oscilloscope 119 by the hybrid electrical/optical transmitter 106, the fiber optic cable 111, the receiver 116 and the electrical cable 117. These signals are first observed without energizing the antennae 102 and 103. The antennae are subsequently energized by signals for differing power and frequencies and the change in signal waveforms appearing at the oscilloscope are observed. Changes in the observed signals with and without the presence of EMI fields serve to identify areas in the DUT 105 that are susceptible.
While illustrative preferred embodiments of the invention have been disclosed herein, many departures from those embodiments may be made without departing from the spirit and scope of the claimed invention. For example, a single ended digital transmitter without common mode rejection may be employed since high frequency (greater than 20 KHz) common mode noise is damped out. Further although discrete component circuitry has been shown, integrated circuits may be employed. For example, the transmitters of FIGS. 2 And 3 could be fabricated with a low cost integrated circuit.
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|Citing Patent||Filing date||Publication date||Applicant||Title|
|US6177804 *||Dec 3, 1998||Jan 23, 2001||Nortel Networks Limited||Common-mode voltage probe for predicting EMI from unshielded differential-pair cables|
|US6400164 *||Jun 22, 2000||Jun 4, 2002||Advanced Micro Devices, Inc.||Method for comparing package EMI performance at multiple clock speeds|
|U.S. Classification||324/72, 324/627, 324/95|